Plasma reactor having digital control over rotation frequency of a microwave field with direct upconversion

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First Claim
1. A plasma reactor comprising:
 a cylindrical microwave cavity overlying a workpiece processing chamber, and first and second coupling apertures in a sidewall of said cylindrical microwave cavity spaced apart by an angle;
a systemcontrolling clock to generate a system clock signal; and
a microwave source having a microwave frequency and comprising a microwave controller having respective microwave outputs coupled to respective ones of said first and second coupling apertures, said microwave controller includingdigital circuitry configured to receive the system clock signal and generate therefrom two digital outputs, at least one of the two digital outputs being a combination of a first component having a first frequency that is lower than the microwave frequency and a second component having a second frequency that is lower than the first frequency,a digitaltoanalog converter coupled to said two digital outputs to generate two analog outputs corresponding to said two digital outputs, andan upconverter coupled to said two analog outputs to convert the two analog outputs to the microwave frequency to provide said microwave outputs.
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Abstract
A plasma reactor for processing a workpiece has a microwave source with a digitally synthesized rotation frequency using direct digital upconversion and a user interface for controlling the rotation frequency.
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16 Claims
 1. A plasma reactor comprising:
a cylindrical microwave cavity overlying a workpiece processing chamber, and first and second coupling apertures in a sidewall of said cylindrical microwave cavity spaced apart by an angle; a systemcontrolling clock to generate a system clock signal; and a microwave source having a microwave frequency and comprising a microwave controller having respective microwave outputs coupled to respective ones of said first and second coupling apertures, said microwave controller including digital circuitry configured to receive the system clock signal and generate therefrom two digital outputs, at least one of the two digital outputs being a combination of a first component having a first frequency that is lower than the microwave frequency and a second component having a second frequency that is lower than the first frequency, a digitaltoanalog converter coupled to said two digital outputs to generate two analog outputs corresponding to said two digital outputs, and an upconverter coupled to said two analog outputs to convert the two analog outputs to the microwave frequency to provide said microwave outputs.  View Dependent Claims (2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13, 14, 15, 16)
1 Specification
This application is a continuation of U.S. patent application Ser. No. 14/974,376, filed Dec. 18, 2015, which claims benefit of U.S. Provisional Application Ser. No. 62/136,737, filed Mar. 23, 2015 and U.S. Provisional Application Ser. No. 62/153,688, filed Apr. 28, 2015, the contents of which are incorporated by reference.
This application is related to a plasma reactor for processing a workpiece such as a semiconductor wafer, using a microwave plasma source.
A plasma generated by a microwave plasma source is characterized with a low sheath voltage and high dissociation of reactive gases. In many applications of microwave plasma processing, circular radial waveguides are conventionally used to make uniform plasmas to process circular wafers. However, the resultant plasma often has an inhomogeneous ion density distribution in either or both the radial direction and the azimuthal direction, owing to a nonuniform field distribution of the microwave applicator, and partly owing to excitation of surface waves.
In order to improve the plasma uniformity, it has been proposed to employ a microwave applicator where the highly uniform field of TE_{111 }mode rotates in a cylindrical cavity adjacent processing region. This is done by introducing microwaves from two spatially orthogonal directions with a temporal phase difference of 90 degrees. To excite a perfectly circular rotation in the circular cavity, phases and amplitudes of electromagnetic waves in the cylindrical cavity are monitored at two orthogonal positions. The measured phase and amplitude are fed back to a dual output digital microwave generator to assure the perfectly circular rotation. In this system of microwave application, the wave fields are circularly rotated inside the cavity, so that a fairly uniform distribution of plasma is expected particularly in the azimuthal direction.
This approach will work for plasmas at low chamber pressures, e.g., pressures less than 200 mTorr. At high pressures (e.g., pressures over 1 Torr, the plasma is often localized, depending upon where the first ignition occurs. In this situation, even though the rotation of the microwave field may be perfectly circular, the localized plasma cannot follow the rotating field, because the rotation period is extremely short corresponding to the microwave frequency. The rotation period may be on the order of about 0.5 ns (e.g., 1/2.45 GHz), which is much less than a global plasma response time (which can exceed 1 ms). It is desired to provide a way of enhancing uniformity in the plasma without impairment from the inability of plasma under high pressure (e.g., 1 Torr) to follow field rotations at 2.45 GHz.
A plasma reactor comprises: a cylindrical microwave cavity overlying a workpiece processing chamber, and first and second coupling apertures in a sidewall of the cylindrical microwave cavity spaced apart by an angle; a microwave source having a microwave frequency and comprising a pair of microwave controllers having microwave outputs coupled to respective ones of the first and second coupling apertures. Each of the microwave controllers comprises (a) a source of first and second digital modulation signals having a frequency corresponding to a slow rotation frequency; (b) a source of a first digital carrier signal having an intermediate frequency; (c) a multiplier stage comprising a pair of multipliers each having a pair of inputs, the multiplier stage coupled to receive, respectively, (a) the first digital modulation signal, the second digital modulation signal and the first digital carrier signal, respectively, the multiplier stage having respective outputs, in1 and in2; and (d) a digitaltoanalog converter coupled to receive the respective outputs in1 and in2 and having analog outputs corresponding to the outputs in1 and in2; and an upconverter having inputs coupled to the analog outputs, the upconverter comprising the microwave outputs.
In one embodiment, a first one of the pair of multipliers is coupled to receive the first digital modulation signal and the digital carrier signal, and having a first multiplier output comprising the output in1, while a second one of the pair of multipliers is coupled to receive the second digital modulation signal and the digital carrier signal, and having a second multiplier output comprising the output in2.
In another embodiment, the reactor further comprises a source of a second digital carrier signal of the intermediate frequency, wherein: the source of the first digital carrier signal is coupled to the output in1; a first one of the pair of multipliers is coupled to receive the first digital modulation signal and the first digital carrier signal; a second one of the pair of multipliers is coupled to receive the second digital modulation signal and the second digital carrier signal, and having a second multiplier output comprising the multiplier output in2; wherein the multiplier stage further comprises an adder coupled to receive outputs of the first and second multipliers, the adder having an output comprising the output in2.
In one embodiment, the first and second amplitude modulation signals comprise, respectively, a cosineform component I and a sineform component Q.
In one embodiment, the source of first and second amplitude modulation signals comprises a first RAM (random access memory) containing successive samples of the cosineform component I, a second RAM containing successive samples of the sineform component Q, and a low clock pointer directed at the successive samples of I and Q in synchronism with the slow rotation frequency.
In one embodiment, the source of a digital carrier signal comprises a third RAM containing successive samples of the digital carrier signal, and a low clock pointer directed at the successive samples of the digital carrier signal in synchronism with the intermediate frequency.
In one embodiment, the upconverter has an output frequency equal to the microwave frequency.
In one embodiment, each of the multipliers produces a product of the signals at its input.
In one embodiment, the plasma reactor further comprises a user interface for allowing a user to specify the slow rotation frequency. In one embodiment, the user interface further allows a user to specify a phase difference between the microwave signal outputs.
In accordance with one embodiment, a method is provided for producing a rotating microwave field in a cavity having a pair of microwave injection ports offset by an angle, having a controlled slow rotation frequency. The method comprises: producing first and second digital carriers of an intermediate frequency below the frequency of the microwave field, the first and second digital carriers being cofunctions of one another; producing at least one of first and second digital modulation signals of a slow frequency corresponding to the slow rotation frequency, the first and second digital modulation signals being corresponding cosineform and sineform components; producing first and second digital carriers of an intermediate frequency below the frequency of the microwave field, the first and second digital carriers being cofunctions of one another; mixing at least the second digital modulation signal with at least one of the first and second digital carriers to produce at least one of a pair of digital outputs in1 and in2; and upconverting the digital outputs to the microwave frequency to produce a pair of offset microwave signals, and applying the pair of offset microwave signals to the pair of microwave injection ports.
In one embodiment, the method further comprises mixing the first and second digital modulation signals with respective ones of the first and second digital carriers to produce respective ones of the pair of digital outputs in1 and in2.
In one embodiment, the method further comprises: providing the first digital carrier signal as the output in1; mixing the first and second digital carriers with respective ones of the first and second digital modulation signals, and adding the corresponding products to produce the output in2.
In accordance with a further aspect employing direct upconversion, a plasma reactor comprises a cylindrical microwave cavity overlying a workpiece processing chamber, and first and second coupling apertures in a sidewall of the cylindrical microwave cavity spaced apart by an angle; a microwave source having a microwave frequency and comprising microwave outputs coupled to respective ones of the first and second coupling apertures. The microwave source comprises a source of an inphase component 1A and of a quadrature component 2A of a digital modulation signal having a frequency corresponding to a slow rotation frequency; a digitaltoanalog converter coupled to receive the inphase and quadrature components 1A and 1B, and having corresponding analog outputs in1 and in2; and an upconverter comprising: (a) a first combiner function comprising respective inputs of the analog output in1 and an inphase component of the microwave frequency, and a first product output corresponding to a first one of the microwave outputs; and (b) a second combiner function comprising respective inputs of the analog output in2 and an inphase component of the microwave frequency, the second combiner function comprising a second product output.
In one embodiment, the second product output is coupled to a second one of the microwave outputs.
In a different embodiment, the microwave source further comprises a source of a constant signal A, and wherein the upconverter further comprises: a third combiner function having one input coupled to receive the constant signal A and another input coupled to receive the quadrature component of the microwave frequency, and a third product output; and an adder function having inputs coupled to the second and third product outputs respectively and a sum output coupled to the second one of the microwave outputs.
In one embodiment, the source of an inphase component of the digital modulation signal produces a sum of the digital modulation signal and the constant signal A.
In one embodiment, the inphase and quadrature components comprise, respectively, a cosineform component I and a sineform component Q. In one embodiment, the source of the inphase component of the digital modulation signal comprises a first RAM containing successive samples of the cosineform component I; the source of the quadrature component of the digital modulation signal comprises a second RAM containing successive samples of the sineform component Q; and a low clock pointer is directed at the successive samples of I and Q in synchronism with the slow rotation frequency.
In one embodiment, the upconverter has an output frequency equal to the microwave frequency.
In one embodiment, each combiner function is adapted to produce a product of the signals at its inputs.
In one embodiment, the angle is 90 degrees.
In one embodiment, the plasma reactor further comprises a user interface for allowing a user to specify the slow rotation frequency. In one embodiment, the user interface further allows a user to specify a phase difference between the respective microwave outputs.
In accordance with a further aspect, in a plasma reactor a cylindrical microwave cavity overlies a workpiece processing chamber, and first and second coupling apertures in a wall of the cylindrical microwave cavity are spaced apart by an angle. A microwave source has a microwave frequency and comprises respective microwave outputs coupled to respective ones of the first and second coupling apertures, the microwave source further comprising a source of an inphase component 2A and of a quadrature component 2B of a digital modulation signal having a frequency corresponding to a slow rotation frequency; a digitaltoanalog converter coupled to receive the inphase and quadrature components 2A and 2B, and having corresponding analog outputs 2Iin and 2Qin; and an upconverter comprising: (a) a first combiner output corresponding to a product of a constant signal A and an inphase component of the microwave frequency, and coupled to a first one of the microwave outputs; (b) a second combiner output corresponding to a product of the analog output 2Iin and an inphase component of the microwave frequency; (c) a third combiner output corresponding to a product of the analog output 2Qin and a quadrature component of the microwave frequency, and an adder having inputs comprising the second and a third combiner outputs and a sum output coupled to a second one of the microwave outputs.
In one embodiment, the inphase and quadrature components comprise, respectively, a cosineform component I and a sineform component Q. In one embodiment, the source of the inphase component of the digital modulation signal comprises a first RAM containing successive samples of the cosineform component I; the source of the quadrature component of the digital modulation signal comprises a second RAM containing successive samples of the sineform component Q; and a low clock pointer is directed at the successive samples of I and Q in synchronism with the slow rotation frequency.
A method of producing a rotating microwave field of a microwave frequency in a cavity having a pair of microwave injection ports offset by an angle, comprises: producing at least one of inphase and quadrature components of a modulation signal of a frequency corresponding to a slow rotation frequency; producing combinations of the inphase component and quadrature component of the modulation signal with at least one of an inphase component or quadrature component of the microwave frequency and producing from the combinations a pair of output signals, and applying the pair of output signals to the pair of microwave injection ports.
In one embodiment, the producing combinations comprises producing: a first product of the inphase component of the modulation signal and the inphase component of the microwave frequency, and a second product of the quadrature component of the modulation signal and the quadrature component of the microwave frequency.
In one embodiment, the method further comprises one of: (a) adding the first and second products to produce one of pair of output signals, or (b) providing the first and second products as the pair of output signals.
In one embodiment, the foregoing method is carried out by a computer programmed to perform the method.
So that the manner in which the exemplary embodiments of the present invention are attained can be understood in detail, a more particular description of the invention, briefly summarized above, may be had by reference to the embodiments thereof which are illustrated in the appended drawings. It is to be appreciated that certain well known processes are not discussed herein in order to not obscure the invention.
To facilitate understanding, identical reference numerals have been used, where possible, to designate identical elements that are common to the figures. It is contemplated that elements and features of one embodiment may be beneficially incorporated in other embodiments without further recitation. It is to be noted, however, that the appended drawings illustrate only exemplary embodiments of this invention and are therefore not to be considered limiting of its scope, for the invention may admit to other equally effective embodiments.
In order to resolve the issue of plasma uniformity at high chamber pressures at which the plasma is unable to follow fast rotations of the microwave field, embodiments described below provide new modes of microwave cavity excitation. A first mode is a slow rotation mode excited by amplitude modulation. A second mode is a slow pulsing mode excited by phase modulation. In these modes, the modulation frequency can be arbitrarily low, typically 0.11000 Hz, which corresponds to the rotation period of 1 ms10 s. At such low rotation frequencies, a localized plasma under high chamber pressure can follow the rotation, thus enabling a uniform distribution of plasma ion density.
Slow Rotation Mode by Amplitude Modulation:
The TE_{111 }mode can be provided by proper selection of the radius and height of the cylindrical cavity 120 at a given angular frequency ω of the dual digital phase and amplitude generator 340. When microwaves are injected through the coupling aperture at P in this condition, clockwise and anticlockwise rotating waves are simultaneously launched with equal probabilities. The axial magnetic field component H_{z }of TE_{111 }mode at a position (r,θ,z) can be written using Bessel function J_{1 }of the first kind as
H_{z}=A[cos(θ−ωt)+cos(θ+ωt)]J_{1}(κr)cos(βz), (1)
where A is the amplitude, β is the axial wave number determined by the cavity height, and κ is the radial wavenumber defined by
Considering the fixed positions of r and z, equation (1) can be rewritten in a normalized form as
η_{P}=a[cos(θ−ωt)+cos(θ+ωt)]=2a cos θ cos ωt. (2)
In the same manner, the wave launched from the coupling aperture at position Q can be written with a phase delay φ as:
η_{Q}=b[sin(θ−ωt+φ−π/2)+cos(θ+ωt−φ−π/2)]=2b sin θ cos(ωt−φ). (3)
In the case of inphase injection (φ=0) of the carrier frequency ω, the simultaneous dual injection from P and Q yields the resultant field:
η=η_{P}+η_{Q}=2(a cos θ+b sin θ)cos ωt. (4)
For slow rotation, the amplitudes a and b are modulated at a low angular frequency Ω_{a }(<<ω) as
a=c cos Ω_{a}t (5)
b=c cos(Ω_{a}t−γ) (6)
where γ is the phase difference in the modulation. Then eq. (4) is reduced to:
η=A cos(Ω_{a}t+ψ)cos ωt (7)
where the amplitude A and the phase ψ are given by
In a special case of
(positive quadrature), a simpler relation applies:
η=2c cos(θ−Ω_{a}t)cos ωt. (10)
In the case of
(negative quadrature), equations (7), (8) and (9) reduce to a similar relation:
η=2c cos(θ+Q_{a}t)cos ωt. (11)
Equations (10) and (11) respectively express the clockwise and anticlockwise rotation of field at the low modulation frequency Ω_{a}.
The foregoing description is provided in terms of the axial magnetic component H_{z}. However, all other components of the magnetic field as well as the electric field rotate together with H_{z}.
To excite the clockwise rotating wave represented by equation 10 (or equation 11), waves launched from P and Q should have forms proportional to equation 5 and equation 6 with the carrier angular frequency ω, and
(or
), respectively:
ζ_{p}=α cos Ω_{a}t cos ωt (12)
and
ζ_{Q}=±α sin Ω_{a}t cos ωt (13)
The wave field inside the cylindrical cavity 120 rotates with the angular frequency Ω_{a}, the direction (clockwise or anticlockwise) depending upon the sign in equation (13). Introducing initial phases φ_{l }for Ω and φ_{h }for ω, equations (12) and (13) can be expressed in a more general form as
ζ_{P}=α cos(Ω_{a}t+φ_{l})cos(ωt+φ_{h})
and
ζ_{Q}=±α sin(Ω_{a}t+φ_{l})cos(ωt+φ_{h})
where φ_{l }and φ_{h }are arbitrary initial phases. Without losing generality, φ_{l }is set at 0 in the remainder of this description, providing the following simplification:
ζ_{P}=α cos Ω_{a}t cos(ωt+φ_{h}) (14)
ζ_{Q}=±α sin Ω_{a}t cos(ωt+φ_{h}). (15)
Conventional analog amplitude modulators can generate the input signals represented by equations (14) and (15). However, in such analog modulators, it is difficult to change the rotation frequency f_{Ω}_{a}=Ω_{a}/2π. Embodiments herein employ a digital controller, such as a field programmable gate array (FPGA) using different random access memories (RAMs) to generate the desired waveforms, in order to this issue. However, to implement equations (14) and (15) in a digital controller, time scale differences between sin Ω_{a}t and cos(ωt+φ_{h}) should be considered carefully. Otherwise, an undesirably large amount of RAM may be required to implement the terms of cos Ω_{a}t and sin Ω_{a}t.
The dual digital phase and amplitude generator 340 generates the microwave signals RF1out and RF2out furnished to the modules Set1 and Set2. The internal structure of the amplitude generator 340 is depicted by the block diagram of
where N_{sys}=2^{n }is the carrier wave modulus and n_{sys }is the count of the carrier wave. The value of n is chosen by the user, and typically n may be in a range of 5 to 7.
The amplitude modulation waves necessary for slow rotation of the microwave field are generated by RAMs 620 and 622 using a low clock of a frequency f_{lclk }(=N_{lclk }f_{Ω}) corresponding to the desired low frequency of rotation. In one embodiment, f_{lclk}=N_{lclk }f_{Ω}. Typically, N_{lclk}=2^{m}. The integer m is arbitrary. One typical choice is N_{sys}=2^{n }N_{lclk}.
The RAM 620 produces a cosineform (inphase) component, I, with the slow wave count n_{lclk }and the slow wave modulus N_{lclk }as
The low clock count n_{lclk }functions as an address pointer to successive locations in the RAM 620 storing successive samples of I.
The RAM 622 produces a sineform (quadrature) component, Q, in accordance with the low clock count n_{lclk }and the low clock modulus N_{lclk }as
The low clock count n_{lclk }functions as an address pointer to successive locations in the RAM 622 storing successive samples of Q.
A digital multiplier 630 combines the cosineform component, I, with the digital IF carrier from the RAM 610 to produce the digital signal in1. A digital multiplier 640 combines the sineform component, Q, with the digital IF carrier from the RAM 610 to produce the digital signal in2.
As described above with reference to
Slow Rotation and Oscillation Mode by Phase Modulation:
Considering the case of constant amplitude a=b in equations (2) and (3), the resultant field becomes:
η=η_{P}+η_{Q}=2a[cos θ cos ωt+sin θ cos(ωt−φ)]. (16)
In a special case of φ=∓
equation (16) reduces to
η=2a cos(θ∓+ωt). (17)
Equation (17) signifies the circular clockwise/anticlockwise rotation at the microwave frequency ω. In this case, the injected microwaves at P and Q are respectively expressed by considering a coupling effect as in equations (12) and (13),
ζ_{P}=α cos(ωt+φ_{h}) (172)
and
ζ_{Q}=±α sin(ωt+φ_{h}). (173)
In case of arbitrary phase φ, equation (16) can be simplified as
η=C cos(ωt+ψ) (18)
where
and
A linear phase modulation may be introduced into equations (18)(20) by introducing the following:
φ=Ω_{p}t(where Ω_{p}<<ω). (21)
In such a case, φ is ramped over time, and the amplitude C expressed in eq. (19) shows different distributions of the microwave field in polar coordinates for successive values of φ as depicted in
Oscillation and slow rotation at a rotation frequency of Ω_{p }is obtained by driving the microwave inputs at locations P and Q of
ζ_{P}=α cos(ωt+φ_{h}) (22)
and
ζ_{Q}=α cos(ωt+φ_{h}−Ω_{p}t)=α[cos(ωt+φ_{h})cos Ω_{p}t+sin(ωt+φ_{h})sin Ω_{p}t] (23)
In this case, the wave in the cavity alternates oscillation and rotation with frequency Ω_{p}, resulting in a pulsing mode.
Conventional analog phase modulation implements equation (22). However, the choice of Ω_{p }is limited. In the digital implementation of equations (22) and (23), the time scale difference between ω and Ω_{p }should be taken into consideration. In order to generate the signals of equations (22) and (23), the FPGA 604 of
where N_{sys}=2^{n }is the carrier wave modulus and n_{sys }is the count of the carrier wave.
The RAMs 620 and 622 store signals generating the linear modulation represented by equation 23 of cos Ω_{p}t and sin Ω_{p}t, where Ω_{p }is the desired slow rotation/oscillation frequency. The respective modulation signals are cofunctions of one another because they contain corresponding sin and cosine terms.
The output of the RAM 610 is used as the digital signal in1. A digital multiplier 660 multiplies the outputs of the RAMs 610 and 620 together. A digital multiplier 662 multiplies the outputs of the RAMs 612 and 622 together. An adder 664 adds the products of the digital multipliers 660, 662 and 663 together and provides the resulting sum as the digital signal in2. The digital signals in1 and in2 thus generated are converted by the digitaltoanalog converter 608 to corresponding analog signals which are processed in the manner described above with reference to
Superposition of the Three Modes:
In the foregoing, three modes have been described: (a) fast rotation mode with angular frequency ω as the carrier frequency (equations (172) and (173)); (b) slow rotation mode with angular frequency Ω (Ω<<ω) (equations (14) and (15)); and (c) slow pulsing mode with angular frequency Ω_{p }with Ω_{p}<<ω (equations (22) and (23)). In the amplitude modulation of equations (14) and (15), for example, one may modify the amplitude as (1+μ sin Ω_{a}t) for the constant μ, and add the phase modulation term −Ω_{p}t, yielding the following set of equations:
ζ_{P}=α cos Ω_{a}t cos(ωt+φ_{h}) (241)
ζ_{Q}=±α(1+μ sin Ω_{a}t)cos(ωt+φ_{h}−Ω_{p}t) (242)
This type of dual injection includes the three rotation modes referred to above. When combining modes (a) and (b), the FPGA of
Direct Digital UpConversion:
In
The digital inphase component corresponding to RFout1 corresponds to the digital input 1A while the digital quadrature component corresponding to RFout1 corresponds to the digital input 1B. Similarly, the digital inphase component corresponding to RFout2 corresponds to the digital input 2A while the digital quadrature component corresponding to RFout2 corresponds to the digital input 2B.
Two DDUP integrated circuits (DDUP ICs) are employed to directly upconvert lowfrequency amplitude modulation signals to a microwave carrier frequency ω. The DDUP IC 6071 combines the analog output 1Iin with an inphase component of the microwave frequency co to produce a first product. The DDUP IC 6071 further combines the analog output 1Qin with a quadrature component of the microwave frequency ω, to produce a second product. The DDUP IC 6071 adds the first and second products to produce the microwave signal RF1out.
The DDUP IC 6072 combines the analog output 2Iin with an inphase component of the microwave frequency co to produce a third product. The DDUP IC 6072 combines the analog output 2Qin with a quadrature component of the microwave frequency ω, to produce a fourth product. The DDUP IC 6072 adds the third and fourth products to produce the microwave signal RF2out. This functionality of each DDUP IC is illustrated in
The FPGA 604 of
In the mode of
which is applied to the digital input 1A of the DAC 608. The DAC converts this signal to an analog amplitude modulation signal B cos Ω_{a}t at the analog output 1Iin. The DDUP IC 6071 mixes the analog modulation signal B cos Ω_{a}t with the microwave frequency inphase component cos(ωt+φ_{h}) to produce the microwave signal RF1out as:
RFout1=αB cos Ω_{a}t cos(ωt+φ_{h}),
where α is a mixinggain, Ω_{a }is the userselected slow rotation frequency and w is the microwave frequency.
In the mode of
which is applied to the digital input 2A of the DAC 608. The DAC 608 converts this signal to an analog amplitude modulation signal B sin Ω_{a}t at the analog output 2Qin. The DDUP IC 6072 mixes the analog modulation signal B sin Ω_{a}t with the microwave frequency inphase component cos(ωt+φ_{h}) to produce the microwave signal RF2out as:
RFout2=αB sin Ω_{a}t cos(ωt+φ_{h}),
where α is a mixinggain, Ω_{a }is the userselected slow rotation frequency and ω is the microwave frequency.
which is applied to the digital input 2A of the DAC 608. The DAC 608 converts this signal to an analog amplitude modulation signal α cos Ω_{a}t at the analog output 2Iin.
The RAM 722 produces a digital quadrature component of an amplitude modulation signal
which is applied to the digital input 2B of the DAC 608. The DAC 608 converts this signal to an analog amplitude modulation signal α sin Ω_{a}t at the analog output 2Qin.
The DDUP IC 6071 mixes the constant, a, received from the output 1Iin, with the microwave frequency inphase component cos(ωt+φ_{h}) to produce the microwave signal RF1out as:
RFout1=α·α cos(ωt+φ_{h}),
where α is a mixinggain, ω is the microwave frequency.
The DDUP IC 6072 mixes the analog modulation signal a·cos Ω_{a}t with the microwave frequency inphase component cos(ωt+φ_{h}) to produce a first product signal
α·a cos Ω_{a}t cos(ωt+φ_{h}),
where α is a mixinggain, Ω_{a }is the userselected slow rotation frequency and ω is the microwave frequency.
The DDUP IC 6072 mixes the analog modulation signal a·sin Ω_{a}t (present at the analog output 2Qin) with the microwave frequency quadrature component sin(ωt+φ_{h}) to produce a second product signal
α·a sin Ω_{a}t sin(ωt+φ_{h}),
where α is a mixinggain, Ω_{a }is the userselected slow rotation frequency and ω is the microwave frequency.
The DDUP IC 6072 adds the first and second product signals to produce the microwave output signal RFout2 as
RFout2=α·[cos Ω_{a}t cos(ωtφ_{h})+cos Ω_{a}t cos(ωtφ_{h})].
which is applied to the digital input 1A of the DAC 608. The DAC 608 converts this signal to an analog amplitude modulation signal A+B cos Ω_{a}t at the analog output 1Iin. The RAM 720 has zero content so that no signal is applied to the digital input 1B of the DAC 608 and no signal is present at the corresponding analog output 1Qin of the DAC 608.
In the mode of
which is applied to the digital input 2A of the DAC 608. The DAC 608 converts this signal to an analog amplitude modulation signal B sin Ω_{a}t at the analog output 2Iin. The RAM 722 outputs a constant, A, which is applied to the digital input 2B of the DAC 608 and is passed through to the analog output 2Qin.
The DDUP IC 6071 mixes the analog amplitude modulation signal A+B cos Ω_{a}t at the analog output 1Iin with the microwave frequency inphase component cos(ωt+φ_{h}) to produce the microwave signal RF1out as:
RFout1=α[A+B cos Ω_{a}t]cos(ωt+φ_{h})
where α is a mixinggain, Ω_{a }is the userselected slow rotation frequency and ω is the microwave frequency.
The DDUP IC 6072 mixes the analog amplitude modulation signal B sin Ω_{a}t at the analog output 2Iin with the microwave frequency inphase component cos(ωt+φ_{h}) to produce a first product signal α B sin Ω_{a}t cos(ωt+φ_{h}), and where α is a mixinggain.
The DDUP IC 6072 mixes the constant A at the analog output 2Qin with the microwave frequency quadrature component sin(ωt+φ_{h}) to produce a second product signal αA sin(ωt+φ_{h}), where α is a mixinggain.
The DDUP IC 6072 adds the first and second product signals together to produce the microwave output signal RF2out as:
RF2out=α[B·sin Ω_{a}t cos(ωt+φ_{h})+A·sin(ωt+φ_{h})]
where α is a mixinggain, Ω_{a }is the userselected slow rotation frequency and ω is the microwave frequency.
The foregoing embodiments may be implemented by a computer (e.g., the computer 602) storing or accessing executable instructions for performing the function of an embodiment described above. The instructions may be accessed from a network or internet connection, from a disk or from other suitable media. By providing access by the computer to the executable instructions for performing the function or method, the computer is said to be programmed to perform the function or method.
Advantages:
Embodiments herein provide uniform processing results across a wide range of chamber pressures by rotating the microwave field of the plasma source. The microwave rotation is digitally synthesized so that the rotation frequency can be set as low as desired to enable the plasma to follow the rotation even at high chamber pressure.
While the foregoing is directed to embodiments of the present invention, other and further embodiments of the invention may be devised without departing from the basic scope thereof, and the scope thereof is determined by the claims that follow.