Asymmetrically fed electric microstrip dipole antenna

• US 3,972,049 A
• Filed: 04/24/1975
• Issued: 07/27/1976
• Est. Priority Date: 04/24/1975
• Status: Expired due to Term

• Current Assignee: the united states of america as represented by the secretary of the navy
• Original Assignee: the united states of america as represented by the secretary of the navy
• Inventors: Kaloi, Cyril M.
• Primary Examiner(s): Lieberman, Eli
• Application Number:
  US05/571,158
• Time in Patent Office: 460 Days
• Field of Search: 343/846, 343/854, 343/829, 343/862
• US Class Current: 343/829
• CPC Class Codes: H01Q 9/0407 Substantially flat resonant element parallel to ground plane, e.g. patch antenna dipole H01Q9/285; monopole H01Q9/40
• CPC Class Codes: H01Q 9/40 Element having extended radiating surface

Abstract

An asymmetrically fed electric microstrip dipole antenna consisting of a n electrically conducting, rectangular-shaped element formed on one surface of a dielectric substrate, the ground plane being on the opposite surface. The length of the element determines the resonant frequency. The feed point is located along the centerline of the antenna length and the input impedance can be varied by moving the feed point along the centerline from the center point to the end of the antenna without affecting the radiation pattern. The antenna bandwidth increases with the width of the element and spacing between the element and ground plane.

Claims

1. An asymmetrically fed electric microstrip dipole antenna having low physical profile and conformal arraying capability, comprising:

a. a thin ground plane conductor;

b. a thin rectangular radiating element spaced from said ground plane;

c. said radiating element being electrically separated from said ground plane by a dielectric substrate;

d. said radiating element having a feed point located along the centerline of the length thereof;

e. said radiating element being fed from a coaxial-to-microstrip adapter, the center pin of said adapter extending through said ground plane and dielectric substrate to said radiating element;

f. the length of said radiating element determining the resonant frequency of said antenna;

g. the antenna input impedance being variable to match most practical impedances as said feed point is moved along said centerline between the antenna radiating element center point and the end of the radiating element in either direction without affecting the antenna radiation pattern;

h. the antenna bandwidth being variable with the width of the radiating element and the spacing between said radiating element and said ground plane, said spacing between the radiating element and the ground plane having somewhat greater effect on the bandwidth than the element width.

2. An antenna as in claim 1 wherein the ground plane conductor extends at least one wavelength beyond each edge of the radiating element to minimize any possible backlobe radiation.

3. An antenna as in claim 1 wherein said thin rectangular radiating element is in the form of a square, said square element being the limit as to how wide the element can be without exciting higher order modes of radiation.

4. An antenna as in claim 1 wherein a plurality of said radiating elements are arrayed to provide a near isotropic radiation pattern.

5. An antenna as in claim 1 wherein the length of said radiating element is approximately 1/2 wavelength.

6. An antenna as in claim 1 wherein said antenna operates to receive and radiate electromagnetic energy in the 1435-1535 MHz and the 2200-2290 MHz bands.

7. An antenna as in claim 1 wherein said thin rectangular radiating element being formed on one surface of said dielectric substrate.

8. An antenna as in claim 1 wherein the length of the antenna radiating element is determined by the equation:

space="preserve" listing-type="equation">A = [1.18 ×

10.sup.10 - F ×

4 ×

H ×

√

ε

]/[2 ×

F ×

√

1 + 0.61 ×

(ε

-

     1) ×

(B/H).sup.0.1155 ]

where

A is the length to be determined

F = the center frequency (Hz)

B = the width of the antenna element

H = the thickness of the dielectric

ε

= the dielectric constant of the substrate.

9. An antenna as in claim 1 wherein the radiation patterns are power patterns, |E.sub.θ

|² and |E.sub.φ

|², polarization field E.sub.φ and

the field normal to the polarization field E.sub.θ

, and are given by the equations;

##EQU14## where U = (U2 - U3)/U5

t = (t3 - t4/t8

u2 = p sin (A ×

P/2) cos (k ×

A ×

sin θ

sin φ

/2)

U3 = k sin θ

sin φ

cos (A ×

P/2) sin (k ×

A ×

sin θ

sin φ

/2)

U5 = (P² - k² sin² θ

sin² φ

)

T3 = P sin (P ×

B/2) cos (k ×

B ×

cos θ

/2)

T4 = k cos θ

cos (P ×

B/2) sin (k ×

B ×

cos θ

/2)

T8 = (P² - k² cos² θ

)

I_m = maximum current (amps) ##EQU15## λ

= free space wave length (inches) λ

_g = waveguide wavelength (inches) and λ

_g = 2 ×

A + (4 ×

H/√

ε

)

r = the range between the antenna and an arbitrary point in space (inches)

Z₀ = characteristic impedance of the element (ohms)

and Z₀ is given by ##EQU16## H = the thickness of the dielectric B = the width of the antenna element

ε

= the dielectric constant of the substrate (no units).

10. An antenna as in claim 1 wherein the minimum width of said radiating element is determined by the equivalent internal resistance of the conductor plus any loss due the dielectric.

11. An antenna as in claim 1 wherein the input impedance, R_in, is given by the equation ##EQU17## where R_a = the radiation resistance

2R_c = the total internal resistance

Z₀ = characteristic impedance of the element, and

Y₀ = distance of feed point from the center of the element.