Corner fed electric microstrip dipole antenna

• US 4,117,489 A
• Filed: 01/23/1978
• Issued: 09/26/1978
• Est. Priority Date: 04/24/1975
• Status: Expired due to Term

• Current Assignee: the united states of america as represented by the secretary of the navy
• Original Assignee: the united states of america as represented by the secretary of the navy
• Inventors: Kaloi, Cyril M.
• Primary Examiner(s): Lieberman, Eli
• Application Number:
  US05/871,573
• Time in Patent Office: 246 Days
• Field of Search: 343/700 MS, 343/829, 343/830, 343/846
• US Class Current: 343/700.0MS
• CPC Class Codes: H01Q 1/286 substantially flush mounted with the skin of the craft
• CPC Class Codes: H01Q 21/205 providing an omnidirectional coverage turnstile aerials H01Q21/26
• CPC Class Codes: H01Q 9/0407 Substantially flat resonant element parallel to ground plane, e.g. patch antenna dipole H01Q9/285; monopole H01Q9/40

Abstract

A corner fed electric microstrip dipole antenna consisting of a thin eleccally conducting, preferably rectangular or square shaped radiating element formed on one surface of a dielectric substrate, the ground plane being on the opposite surface. The feed point is located at one corner of the antenna element and the input impedance is matched with a matching microstrip transmission feed line connected to the corner of the antenna. The length of the element determines the resonant frequency along the Y axis and the width determines the resonant frequency along the Z axis. This antenna is capable of generating circular polarized radiation using a single element and single feed point.

Claims

1. A corner fed electric microstrip dipole antenna having low physical profile and conformal arraying capability, comprising:

a. a thin ground plane conductor;

b. a thin square radiating element spaced from said ground plane;

c. said radiating element being electrically separated from said ground plane by a dielectric substrate;

d. said radiating element having a feed point located at a single corner thereof;

e. the length and width of said radiating element being equal and determining the resonant frequency along the length and width, respectively, of said antenna;

f. the antenna bandwidth being variable with the width dimension of the radiating element and the spacing between said radiating element and said ground plane, said spacing between the radiating element and the ground plane having somewhat greater effect on the bandwidth than the element width, the physical length of said radiating element being changed accordingly with the width thereof to maintain a square radiating element as the physical width is changed to vary the bandwidth; and

g. the polarization of said antenna being linear along the diagonal on which the feedpoint lies and the resonant frequencies being equal along both the length of the antenna and along the width of the antenna with zero phase difference between the two modes of oscillation.

2. An antenna as in claim 1 wherein the ground plane conductor is at least one wavelength long and one wavelength wide to minimize any possible backlobe radiation.

3. An antenna as in claim 1 wherein:

a. a matching microstrip transmission line is provided having one end thereof connected to the radiating element feed point; and

b. said radiating element is operable to be fed from a coaxial-to-microstrip adapter via said matching microstrip transmission line, the center pin of said adapter extending through said ground plane and dielectric substrate to the other end of said matching microstrip transmission line.

4. An antenna as in claim 1 wherein a plurality of said radiating elements are arrayed about a substantially cylindrical body to provide a near isotropic radiation pattern.

5. An antenna as in claim 1 wherein the length of said radiating element is approximately 1/2 wavelength.

6. A square corner fed antenna as in claim 1 wherein said antenna operates in an degenerate mode, said radiating element oscillating in two orthogonal modes of current oscillation with the first mode being along the length and the second being made along the width thereof, the resonant frequency of each mode being the same and the phase difference between the two oscillations being zero, the resultant electric field vector being along the diagonal and in line with the feed corner.