Foreign object detection in wireless energy transfer systems
First Claim
1. A wireless energy transfer system, comprising:
- a source resonator configured to generate an oscillating magnetic field to transfer energy to a receiver resonator;
a plurality of sensors, wherein each of the sensors is configured to generate an electrical signal in response to a magnetic field; and
a controller coupled to each of the sensors,wherein during operation of the system, the controller is configured to;
obtain a system calibration state comprising a set of basis vectors derived from a first set of electrical signals generated by the plurality of sensors with no foreign object debris in proximity to the system;
measure a second set of electrical signals generated by the plurality of sensors;
calculate a projection of the second set of electrical signals onto the set of basis vectors;
calculate a detection signal based on the projection of the second set of electrical signals;
determine whether foreign object debris is present in proximity to the system by comparing the calculated detection signal to a detection threshold value; and
adjust the system calibration state based on the presence or absence of foreign object debris in proximity to the system to generate an updated system calibration state.
1 Assignment
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Accused Products

Abstract
The disclosure features wireless energy transfer systems that include a plurality of sensors coupled to a controller, wherein the controller is configured to: obtain a system calibration state including a set of basis vectors derived from a first set of electrical signals generated by the plurality of sensors with no foreign object debris in proximity to the system; measure a second set of electrical signals from the sensors; calculate a projection of the second set of electrical signals onto the set of basis vectors; calculate a detection signal based on the projection; determine whether foreign object debris is present in proximity to the system by comparing the calculated detection signal to a detection threshold value; and adjust the system calibration state based on the presence or absence of foreign object debris in proximity to the system to generate an updated system calibration state.
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20 Claims
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1. A wireless energy transfer system, comprising:
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a source resonator configured to generate an oscillating magnetic field to transfer energy to a receiver resonator; a plurality of sensors, wherein each of the sensors is configured to generate an electrical signal in response to a magnetic field; and a controller coupled to each of the sensors, wherein during operation of the system, the controller is configured to; obtain a system calibration state comprising a set of basis vectors derived from a first set of electrical signals generated by the plurality of sensors with no foreign object debris in proximity to the system; measure a second set of electrical signals generated by the plurality of sensors; calculate a projection of the second set of electrical signals onto the set of basis vectors; calculate a detection signal based on the projection of the second set of electrical signals; determine whether foreign object debris is present in proximity to the system by comparing the calculated detection signal to a detection threshold value; and adjust the system calibration state based on the presence or absence of foreign object debris in proximity to the system to generate an updated system calibration state. - View Dependent Claims (2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13, 14, 15, 16, 17)
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18. A method, comprising:
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determining a system calibration state comprising an inverse covariance matrix for a first set of electrical signals generated by a plurality of sensors in proximity to a wireless energy transfer system when no foreign object debris is in proximity to the wireless energy transfer system; determining a set of basis vectors from eigenvectors of the inverse covariance matrix; measuring a second set of electrical signals generated by the plurality of sensors; calculating a detection signal based on a projection of the second set of electrical signals onto the set of basis vectors; determining whether foreign object debris is present in proximity to the wireless energy transfer system by comparing the calculated detection signal to a detection threshold value; and adjusting the system calibration state based on the presence or absence of foreign object debris in proximity to the system to generate an updated system calibration state. - View Dependent Claims (19, 20)
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1 Specification
This application claims priority to the following U.S. Provisional patent applications, the entire contents of each of which are incorporated herein by reference: 62/243,469, filed on Oct. 19, 2015; 62/267,009, filed on Dec. 14, 2015; 62/309,840, filed on Mar. 17, 2016; 62/261,077, filed on Nov. 30, 2015; and 62/376,497, filed on Aug. 18, 2016.
This disclosure relates wireless energy transfer systems and detection of foreign object debris (FOD) in the vicinity of such systems.
Energy or power may be transferred wirelessly using a variety of known radiative, or far-field, and non-radiative, or near-field, techniques as detailed, for example, in commonly owned U.S. Patent Application Publication Nos. 2010/01099445, 2010/0308939, 2012/0062345, and 2012/0248981, the entire contents of each of which are incorporated herein by reference.
This disclosure features methods and systems for detecting FOD in proximity to wireless energy transfer systems. In particular, the methods and systems can be used with wireless energy transfer systems that use magnetic resonators to transfer power via oscillating magnetic fields. Such systems can transfer large quantities of power, and the presence of FOD can represent a particular hazard during operation. The methods and systems disclosed herein can also be used with other types of wireless energy transfer systems as well, including resonant and non-resonant systems, and systems that transfer power via electromagnetic fields.
The systems and methods disclosed herein use a principal components-based analysis to identify FOD and to update calibration settings to correct for drift due to a variety of sources. Measurements from one or more FOD sensors are transformed into a principal components basis derived from an inverse covariance matrix describing a system calibration state, in such a way that the first principal component represents a multi-dimensional direction corresponding to the largest variance, with succeeding principal components representing directions of successively smaller variance. The principal components therefore represent the data in an uncorrelated, orthogonal basis vector set. When a foreign object is present in proximity to the system, the basis-projected sensor measurements are scattered most strongly in the direction of the first principal component. This has the advantage of increasing the sensitivity of the system to small FOD, and FOD located at relatively large vertical distances from the wireless energy source.
Principal components (PC) analysis of the FOD sensor measurements can provide a number of additional advantages. For example, fast calibration routines can be used to generate an initial system calibration and ongoing updates to the calibration, so that the system is ready for use shortly after initialization. FOD detection signals can be calculated rapidly, allowing for fast signaling by the system when potential FOD is identified. Projection of sensor measurements into the PC basis also allows the measured signals to be used for alignment of the source and receiver in a wireless energy transfer system. For example, for vehicle-based charging, the sensor measurements can be used during vehicle parking to ensure alignment of a vehicle mounted receiver and a ground-based source so that vehicle charging occurs efficiently after parking is complete.
In a first aspect, the disclosure features wireless energy transfer systems that include: a source resonator configured to generate an oscillating magnetic field to transfer energy to a receiver resonator, a plurality of sensors, where each of the sensors is configured to generate an electrical signal in response to a magnetic field, and a controller coupled to each of the sensors, where during operation of the system, the controller is configured to: obtain a system calibration state comprising a set of basis vectors derived from a first set of electrical signals generated by the plurality of sensors with no foreign object debris in proximity to the system; measure a second set of electrical signals generated by the plurality of sensors; calculate a projection of the second set of electrical signals onto the set of basis vectors; calculate a detection signal based on the projection of the second set of electrical signals; determine whether foreign object debris is present in proximity to the system by comparing the calculated detection signal to a detection threshold value; and adjust the system calibration state based on the presence or absence of foreign object debris in proximity to the system to generate an updated system calibration state.
Embodiments of the systems can include any one or more of the following features.
The controller can be configured to obtain the system calibration state by: determining an inverse covariance matrix for the first set of electrical signals; and determining the set of basis vectors by determining a set of eigenvectors of the inverse covariance matrix. The controller can be configured to determine the inverse covariance matrix based on mean-subtracted values derived from the first set of electrical signals. The values can include at least one of amplitudes of the first set of electrical signals and phases of the first set of electrical signals.
The plurality of sensors can include n sensors, and each of the basis vectors can include n elements. For each basis vector, each of the n elements can correspond to a contribution from a different one of the n sensors. The projection can include a vector of length p<n, and each element of the projection can correspond to a contribution of a different one of the basis vectors to a representation of the second set of electrical signals. The controller can be configured to calculate the detection signal as a norm of the projection, e.g., as a scaled norm of the projection in which each element of the projection is scaled according an eigenvalue associated with a corresponding one of the basis vectors.
The controller can be configured to adjust the system calibration state when foreign object debris is not in proximity to the system, e.g., by generating an updated inverse covariance matrix based on the second set of electrical signals. The controller can be configured to generate the updated inverse covariance matrix using an infinite impulse response filter.
Prior to obtaining the system calibration state, the controller can be configured to determine whether foreign object debris is present in proximity to the system. The controller can be configured to determine whether foreign object debris is present in proximity to the system prior to obtaining the system calibration state by: measuring a plurality of sets of electrical signals generated by the plurality of sensors, where each set of electrical signals corresponds to a different relative position of the source and receiver resonators; generating a position covariance matrix based on the plurality of sets of electrical signals; determining a set of position basis vectors corresponding to eigenvectors of an inverse of the position covariance matrix; measuring a third set of electrical signals generated by the plurality of sensors; calculating a projection of the third set of electrical signals onto the set of position basis vectors; and determining whether foreign object debris is present in proximity to the system based on a magnitude of the projection of the third set of electrical signals. The set of position basis vectors can correspond to a set of m eigenvectors of the inverse of the position covariance matrix that correspond to m largest eigenvalues of the inverse of the position covariance matrix.
Each of the plurality of sensors can include one or more loops of conducting material. At least some of the sensors can include a first loop of conducting material coupled to a second loop of conducting material. The first and second loops may not overlap. The first and second loops can be configured so that when a magnetic field flux density through the first and second loops is the same, the first and second loops generate electrical signals of approximately equal magnitude.
At least one of the sensors can include a first loop of conducting material featuring two terminals and a second loop of conducting material featuring two terminals, where a second terminal of the first loop is directly connected to a first terminal of the second loop, and a second terminal of the second loop is not connected to either terminal of the first loop. When magnetic field flux extends through the first and second loops, the controller can be configured to measure a reference electrical signal by measuring an electrical signal between the terminals of the first loop, and the controller can be configured to measure an electrical signal featuring contributions from both the first and second loops by measuring an electrical signal between a first terminal of the first loop and the second terminal of the second loop.
The plurality of sensors can be positioned so that when the source resonator generates the oscillating magnetic field, the sensors generate the electrical signals based on a portion of the oscillating magnetic field that extends through the sensors.
The systems can include an auxiliary coil connected to the controller and configured to generate a measurement magnetic field in a spatial region in proximity to at least one of the source and receiver resonators. The plurality of sensors can be positioned so that when the auxiliary coil generates the measurement magnetic field, the sensors generate the electrical signals based on a portion of the measurement magnetic field that extends through the sensors.
The plurality of sensors comprises an array of loops of conductive material in which each loop of the array is coupled to another loop of the array.
The first and second loops can be coupled through a direct electrical connection between the loops. The first and second loops can be coupled through a hardware or software processor, and the processor can be configured to invert an electrical signal generated by one of the first and second loops.
Obtaining the system calibration state can include retrieving the system calibration state from an electronic storage medium. Obtaining the system calibration state can include: determining an inverse covariance matrix for the first set of electrical signals; determining a set of eigenvectors of the inverse covariance matrix; and determining the set of basis vectors from the eigenvectors of the inverse covariance matrix.
Embodiments of the systems can also include any of the other features disclosed herein, including features disclosed in connection with different embodiments, in any combination as appropriate.
In another aspect, the disclosure features methods that include: determining a system calibration state featuring an inverse covariance matrix for a first set of electrical signals generated by a plurality of sensors in proximity to a wireless energy transfer system when no foreign object debris is in proximity to the wireless energy transfer system; determining a set of basis vectors from eigenvectors of the inverse covariance matrix; measuring a second set of electrical signals generated by the plurality of sensors; calculating a detection signal based on a projection of the second set of electrical signals onto the set of basis vectors; determining whether foreign object debris is present in proximity to the wireless energy transfer system by comparing the calculated detection signal to a detection threshold value; and adjusting the system calibration state based on the presence or absence of foreign object debris in proximity to the system to generate an updated system calibration state.
Embodiments of the methods can include any one or more of the following features.
The methods can include determining the inverse covariance matrix based on values derived from the first set of electrical signals, where the values include at least one of amplitudes of the first set of electrical signals and phases of the first set of electrical signals. The plurality of sensors can include n sensors, and each of the basis vectors can include n elements each corresponding to a contribution from a different one of the n sensors.
The projection can include a vector of length p<n, and each element of the projection can correspond to a contribution of a different one of the basis vectors to a representation of the second set of electrical signals. Calculating the detection signal can include determining a norm of the projection.
The methods can include adjusting the system calibration state when foreign object debris is not in proximity to the system. The methods can include adjusting the system calibration state by generating an updated inverse covariance matrix based on the second set of electrical signals. The methods can include generating the updated inverse covariance matrix using an infinite impulse response filter. The methods can include, prior to determining the system calibration state, determining whether foreign object debris is present in proximity to the wireless energy transfer system.
Embodiments of the methods can also include any of the other features disclosed herein, including features disclosed in connection with different embodiments, in any combination as appropriate.
As used herein, “foreign object debris” (FOD) refers to objects formed of materials that, when exposed to a field used for wireless energy transfer, undergo significant heating and/or interaction with the field. For example, for resonant wireless energy transfer systems that use oscillating magnetic fields to transfer energy, FOD formed of materials such as metals can interact strongly with the energy transfer fields. In particular, the magnetic fields can induce eddy currents in metallic objects; if the fields are sufficiently large, the amount of heat generated in the metallic objects due to the induced currents can cause the objects to ignite. As such, for high energy wireless transfer systems in particular, the presence of nearby FOD can represent a significant operating hazard. In addition, coupling between the energy transfer field and the FOD reduces the amount of energy that is transferred to the system'"'"'s receiver. Thus, in addition to posing a potential safety hazard, FOD also reduces the energy transfer efficiency of the system.
As used herein, “wireless energy transfer” from one resonator to another refers to transferring energy to do useful work (e.g., mechanical work) such as powering electronic devices, vehicles, lighting a light bulb or charging batteries. Similarly, “wireless power transmission” from one resonator to another refers to transmitting power to do useful work (e.g., mechanical work) such as powering electronic devices, vehicles, lighting a light bulb or charging batteries. Both wireless energy transfer and wireless power transmission refer to the transfer of energy (or the transmission of power) to provide operating power that would otherwise be provided through a connection to a power source, such as a connection to a mains voltage source. Accordingly, with the above understanding, the expressions “wireless energy transfer” and “wireless power transmission” are used interchangeably in this disclosure. It should also be understood that “wireless power transmission” and “wireless energy transfer” can be accompanied by the transfer of information; that is, information can be transferred via an electromagnetic signal along with the energy or power to do useful work.
Unless otherwise defined, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this disclosure belongs. Although methods and materials similar or equivalent to those described herein can be used in the practice or testing of the subject matter herein, suitable methods and materials are described below. All publications, patent applications, patents, and other references mentioned herein are incorporated by reference in their entirety. In case of conflict, the present specification, including definitions, will control. In addition, the materials, methods, and examples are illustrative only and not intended to be limiting.
The details of one or more embodiments are set forth in the accompanying drawings and the description below. Other features and advantages will be apparent from the description, drawings, and claims.
Like reference symbols in the various drawings indicate like elements.
Introduction
Wireless energy transfer systems that generate an oscillating magnetic field to transfer energy between two coupled resonators (i.e., a source resonator and a receiver resonator) can be efficient, non-radiative, and safe. Certain non-magnetic and/or non-metallic objects that are inserted between the resonators may not substantially interact with the magnetic field used for wireless energy transfer. However, certain objects—such as some metallic objects, for example—inserted between the resonators may interact with the magnetic field of the wireless power transfer system in a way that causes the objects to perturb the wireless energy transfer and/or to heat up substantially. Detection of the presence of such objects in proximity to wireless energy transfer systems is therefore desirable, as detection can be followed by actions such as reducing the amount of energy that is transferred (or even discontinuing energy transfer entirely), and alerting a user of the system that such objects are present.
Objects that perturb the wireless energy transfer are referred to herein as foreign object debris (FOD). As noted above, some FOD may interact with the energy transfer magnetic field in a way that may perturb the characteristics of the resonators used for energy transfer, may block or reduce the magnetic fields used for energy transfer, or may create a fire and/or burning hazard. In some applications, special precautions may be necessary to avoid combustible metallic objects becoming hot enough to ignite during high power energy transfer. Some metallic objects can heat up and have enough heat capacity to burn or cause discomfort to a person who might pick them up while they are still hot. Examples include tools, coils, metal pieces, soda cans, steel wool, food packaging, and tobacco packaging.
In similar fashion, receiver resonator 104 is coupled to a load 108 through a coupling 107. Coupling 107 can be a direct electrical connection or a non-contact inductive coupling. In some embodiments, coupling 107 can include an impedance matching network, as described above.
In general, load 108 receives power from receiver resonator 104. Device 108 then uses the power to do useful work. In some embodiments, for example, load 108 is a battery charger or manager that charges one or more batteries of a vehicle (e.g., car, truck, etc.) In some embodiments, load 108 can be a battery of the vehicle.
During operation, source resonator 102 is configured to wirelessly transmit power to receiver resonator 104. In some embodiments, source resonator 102 can generate oscillating fields (e.g., electric, magnetic fields) when supplied with electrical power from power supply 106. The oscillating fields couple to receiver resonator 104 and provide power to the receiver resonator 104 through the coupling. More specifically, the oscillating fields generated by source resonator 102 can induce oscillating currents within receiver resonator 104. In some embodiments, either or both of the source and receiver coils can be configured to be resonant. In certain embodiments, either or both of the source and receiver coils can be non-resonant so that the power transfer is achieved through non-resonant coupling.
In certain embodiments, the system 100 can include a power repeating apparatus (not shown in
System 100 includes electronic controllers 103a and 103b (which together form a control system) configured to control power transfer in system 100, for example, by directing power supply 106 to drive source resonator 102 with an oscillating electrical current. In general, electronic controller 103a (the source-side controller) is connected to source resonator 102 and power supply 106 via connections 109a. Where coupling 105 includes components such as an impedance matching network, electronic controller 103a can also be connected to coupling 105 via a connection 109a.
Electronic controller 103b is connected to receiver resonator 104 and load 108 via connections 109b. Where coupling 107 includes components such as an impedance matching network, electronic controller 103b can also be connected to coupling 107 via a connection 109b. Electronic controller 103a can also be connected to electronic controller 103b via a wired or wireless connection 109c.
In some embodiments, some or all of connections 109a-b are wired connections. In certain embodiments, some or all of connections 109a-b are wireless connections (e.g., radio-frequency, Bluetooth communication). The nature of connections 109a-b can depend on the various components of system 100. For example, electronic controller 103a can be connected to power supply 106 and/or coupling 105 and/or source resonator 102 via wired connections 109a, and connected to electronic controller 103b via a wireless connection 109c. Similar considerations apply to electronic controller 103b.
Electronic controller 103a can configure power supply 106 to provide power to source resonator 102, and to regulate the output of supply 106 to adjust the magnitude of the energy transfer field generated by source resonator 102. The driving current from supply 106 can be at an oscillation frequency that corresponds to a frequency of the energy transfer field generated by source resonator 102.
In some embodiments, electronic controllers 103a and 103b can tune the resonant frequencies of the source resonator 102 and/or the receiver resonator 104 (e.g., by tuning reactive components of impedance matching networks) to regulate energy transfer efficiency, the amount of energy transferred, to mitigate positional offsets between the resonators, and/or for other reasons as well. Adjustments can be based on measurement of a frequency of the energy transfer field generated by source resonator 102, and/or based on measurements of current and/or voltage (and magnitudes and/or phases thereof) in either resonator, for example, by one or more sensors connected to electronic controllers 103a and/or 103b. In certain embodiments, electronic controllers 103a and 103b can tune the resonant frequencies of one or both of source resonator 102 and receiver resonator 104 to be substantially the same (e.g., within 0.5%, within 1%, within 2%).
In certain embodiments, electronic controllers 103a and 103b can adjust impedance matching conditions in system 100 by adjusting one or more resistive, capacitive, and/or inductive elements in an impedance matching network that is part of coupling 105, and/or in an impedance matching network that is part of coupling 107. Adjusting the impedance matching conditions controls the efficiency of energy transfer between resonators 102 and 104, and can be performed iteratively by electronic controller 103 based on measurements of voltage, current, and other performance-related parameters by one or more sensors connected to controllers 103a and/or 103b.
In addition to source resonator 102 and receiver resonator 104, in some embodiments, system 100 can include one or more repeater resonators that function as active or passive relays, receiving power from one resonator and transferring power to another resonator. In resonant energy transfer systems that use oscillating magnetic fields to transfer power, each of the resonators (e.g., source resonator 102, receiver resonator 104, and any repeater resonators) can have a resonant frequency f=ω/2π, an intrinsic loss rate F, and a Q-factor Q=ω/(2Λ) (also referred as “intrinsic” Q-factor in this disclosure), where ω is the angular resonant frequency. A resonant frequency f of a resonator, for example, in a power source or power receiver of the system, can have a capacitance and inductance that defines its resonant frequency f.
To achieve high efficiency wireless energy transfer, which is particularly important for applications such as vehicle charging where large amounts of energy are transferred to charge a vehicle'"'"'s onboard battery system, some or all of the resonators in system 100 have a relatively high Q-factor. For example, the Q-factor of some or all of the resonators can be greater than 100 (e.g., Q>200, Q>300, Q>500, Q>1000).
Utilizing high Q-factor resonators can lead to large energy coupling between some or all of the resonators in a wireless power transfer system. The high Q factors can lead to strong coupling between resonators such that the “coupling time” between the resonators is shorter than the “loss time” of the resonators. In this approach, energy can be transferred efficiently between resonators at a faster rate than the energy loss rate due to losses (e.g., heating loss, radiative loss) of the resonators. In certain embodiments, a geometric mean √{square root over (QiQj)} can be larger than 100 (e.g., √{square root over (QiQj)}>200, √{square root over (QiQj)}>300, √{square root over (QiQj)}>500, √{square root over (QiQj)}>1000) where i and j refer to a source-receiver resonator pair, a source-repeater resonator pair, or a repeater-receiver resonator pair. Additional aspects of high-Q resonators are disclosed, for example, in U.S. Pat. No. 8,461,719, the entire contents of which are incorporated herein by reference.
System 200 also includes a receiver resonator 214, an impedance matching network 216, a rectifier 218, a DC/DC and/or DC/AC converter 220, and a device 222. These components are connected to one another via direct wired connections, and are also connected to controller 212b via connections 215.
Power supply 202 can be an AC voltage source such as a home electrical outlet or a DC voltage source such as a battery. The power supply 202 delivers a current to converter 204, which converts the current to a direct current (i.e., a DC current). The direct current is amplified by power inverter or amplifier 206 to generate a driving current that drives source resonator 210. The oscillation frequency and amplitude of the driving current can be adjusted by power amplifier 206 (under the control of controller 212) to control the magnetic field generated by source resonator 210.
Impedance matching network (IMN) 208 adjusts the impedance of source resonator 210. For example, IMN 208 can be tuned (e.g., by controller 212) to adjust for the perturbation of the quality factor Q of the source resonator 210 due to the presence of FOD in proximity to the resonator. IMN 208 can also be tuned to regulate energy transfer between source and receiver resonators 210 and 214, e.g., based on feedback signals measured by one or more sensors (not shown in
IMN 208 can include a capacitor or networks of capacitors, an inductor or networks of inductors, or any combination of capacitors, inductors, diodes, switches, resistors, and similar elements. The components of the impedance matching network may be adjustable and variable and may be controlled to affect the efficiency and operating point of the system. Impedance matching may be performed by controlling the connection point of the resonator, adjusting the permeability of a magnetic material, controlling a bias field, adjusting a frequency of excitation, and similar operations, all of which are carried out by controller 212. Elements of IMN 208 that can be tuned and controlled by controller 212 include any number or combination of varactors, varactor arrays, switched elements, capacitor banks, switched and tunable elements, reverse bias diodes, air gap capacitors, compression capacitors, BZT electrically tuned capacitors, MEMS-tunable capacitors, voltage variable dielectrics, pulse-width modulation (PWM) controlled capacitors, barium strontium titanate (BST) capacitors, and transformer coupled tuning circuits. Variable components can be mechanically tuned, thermally tuned, electrically tuned, and piezo-electrically tuned.
The driving current supplied by power amplifier 206 causes source resonator 210 to generate an oscillating magnetic field at a frequency that matches or nearly matches a resonance frequency of receiver resonator 214. Receiver resonator 214 captures a portion of the field, which induces an oscillating current (i.e., an AC current) in the receiver resonator.
IMN 216 on the receiver side of system 200 functions in a manner similar to IMN 208. The AC current in receiver resonator 214 is rectified by rectifier 218, and then converted into a DC or AC output current by converter 220, and delivered to device 222, where the current is used to perform useful work such as charging a vehicle battery system. Additional aspects and features of the various components of system 200 are disclosed, for example, in the following U.S. Patent Application Publications, the entire contents of each of which are incorporated herein by reference: 2015/0270719; 2013/0069441; 2014/0111019; and 2015/0323694.
To detect FOD, the wireless energy transfer systems disclosed herein include one or more FOD sensors.
System 300 also includes the other source-side components shown in
Also connected to controller 308 via a connection line 310a are one or more FOD sensors 310. In the following discussion, FOD sensors 310 will be referred to as an “array” of FOD sensors. It should be understood that the array can include any number of sensors, including a single sensor. Typically, however, system 300 includes multiple FOD sensors as part of the array.
It should also be understood that the term array, when applied to described sensors 310, does not necessarily mean that sensors 310 are arranged in a regular pattern or geometric shape. FOD sensors 310 can, in some embodiments, be arranged in a regular pattern (e.g., a square, rectangular, or hexagonal pattern). In certain embodiments, however, some or all of FOD sensors 310 are located such that they do not form a regular pattern. In general, individual FOD sensors 310 can be positioned at any x-y location and any elevation z between source resonator 302 and receiver resonator 304. The “array” of FOD sensors 310 can include individual sensors and/or groups of sensors positioned at different elevations, and sensors positioned at any x-y location. Multiple “layers”—each featuring multiple FOD sensors, and each at a different z elevation—can collectively correspond to the array of FOD sensors 310.
Each of the FOD sensors 310 in the array is connected to controller 308 and transmits its measurement signal to controller 308. In turn, controller 308 receives the measurement signals and uses the signals to establish baseline readings and identify the presence of FOD in the vicinity of system 300. For vehicle charging applications, system 300 can operate—at a particular time—in one of several modes, depending upon the positional relationship between the vehicle and the system. A first mode, for example, corresponds to the situation where the vehicle is approaching the wireless energy transfer system but has not yet parked, and power is not yet being transferred to the vehicle'"'"'s on-board battery system. In this mode, low power diagnostic tests can be conducted without the vehicle present to check the status of the system and to check for FOD prior to the arrival of the vehicle.
A second mode corresponds to the situation where the vehicle has parked in proximity to source resonator 302, such that source resonator 302 and receiver resonator 304 are aligned, or approximately aligned. However, transfer of energy between source resonator 302 and receiver resonator 304, e.g., to charge the vehicle'"'"'s batteries, is not yet occurring. In this mode, system 300 determines whether the region in proximity to source resonator 302 and/or receiver resonator 304 is free of FOD.
A third mode corresponds to the situation where energy is being transferred from source resonator 302 to receiver resonator 304, e.g., to charge the batteries of vehicle 312. During energy transfer at high power levels, system 300 uses measurements from sensor array 310 to ensure that no new FOD has arrived in the system in proximity to source resonator 302.
A wide variety of different FOD sensors 310 can be used to measure signals for FOD detection. Examples of suitable sensors will be discussed in greater detail in a later section of this disclosure.
FOD Detection by Principal Components Analysis
The systems and methods disclosed herein involve detection of FOD by principal components (PC) analysis. The PC basis provides a convenient space to represent measurements from FOD sensors in a non-local, orthogonal, uncorrelated set of basis vectors, organized according to their relative information content. A relatively small number of basis vectors can be used to represent the sensor environment (e.g., the distribution of magnetic fields within in proximity to the source and receiver resonators). The PC basis representation of the measured FOD sensor signals naturally de-noises the signals and calibration states that are produced from the signals. Furthermore, the projection of the sensor measurements into the PC basis allows the information encoded in the measurements to analyzed using a variety of techniques.
The principal components encode sensor measurements in a global manner; each principal component includes signal contributions from each of the FOD sensors in the system. The components can then be ordered according to their relative information content with respect to FOD detection. Put another way, the transformation from measurement signals to principal components is performed such that the first principal component represents the “direction” in the measurement signal data corresponding to the largest variance. Each successive principal component corresponds to the direction in the signal data corresponding to the next-largest variance. By transforming the measurement signal data in this manner, the set of principal components thus obtained constitutes an uncorrelated and orthogonal basis vector set.
The PC basis set can be updated to follow slow drift in the system calibration due to factors such as drift in the source-side power amplifier, and longer term changes in the electromagnetic environment in proximity to the system. As such, the system calibration can be dynamically updated to reduce the incidence of false-positive FOD detection. When FOD is present in proximity to the system, the electromagnetic environment changes in a way that scatters the FOD sensor measurements, as projected in the PC basis, far from the baseline system calibration. The scattering allows for robust FOD detection, and is typically represented by growth in the vector distance of the perturbed FOD sensor measurements, projected in the PC basis, from the baseline calibration state.
A number of advantages can be realized by using the PC-based anomaly (e.g., FOD) detection methods disclosed herein. The methods typically yield increased sensitivity to small FOD and FOD located at a variety of different z-elevations (including relatively large z-elevations), relative to conventional FOD detection methods. Natural system drift and noise when no FOD is present typically has some correlation. However, the introduction of FOD in proximity to the system causes perturbations to the electromagnetic environment which do not share the same correlation structure as system drift and noise. As such, the perturbations caused by FOD are isotropic in the spaced defined by the PC basis vectors.
Because the PC basis vectors—which are derived from the inverse covariance matrix—are ordered from highest to lowest variance, relatively small perturbations in the electromagnetic environment affect the contributions of first few PC basis vectors (i.e., those that correspond to the highest variance) to the system state the most. Thus, the PC-based detection methods disclosed herein are designed to focus in particular on FOD-induced perturbations, and to be relatively insensitive to significant but relatively constant contributions to the electromagnetic environment arising from other correlated system features, e.g., drift and noise.
The PC-based methods disclosed herein also permit relatively short system startup and calibration times to be realized. Updates to the system'"'"'s baseline calibration can be performed using fast calibration routines that are performed in real time or near real time. Similarly, after FOD sensor measurements are received by the system controller, calculation of the detection signal by the controller is rapid, allowing for subsequent actions (such as reducing or discontinuing energy transfer, and/or alerting system users) to occur quickly.
The methods can also use FOD sensor measurements, transformed into the PC basis, for localizing the receiver resonator relative to the source resonator. For vehicle charging applications, for example, the system controller can transmit tracking and/or guidance signals to the vehicle on which the receiver resonator is mounted, to assist the vehicle'"'"'s driver during parking to ensure that once parked, energy can be efficiently transferred from the source resonator to the receiver resonator.
Next, in step 408, the FOD detection signal is compared to a detection threshold to determine whether FOD is present in proximity to the system. If FOD is determined to be present, then in optional step 410, the system can take a variety of actions including modifying system operating parameters (e.g., reducing or discontinuing energy transfer between the source and receiver resonators), and issuing various alerting messages and signals to system users.
In step 412, if no FOD is present, the system calibration is updated based on the latest FOD sensor measurements. Control then passes to decision step 414, where the system determines whether FOD detection should continue. If so, control returns to step 404 and new FOD sensor measurements are obtained. If not, the procedure ends at step 416.
The steps in flow chart 400 will now be individually discussed in greater detail. To facilitate the discussion, Table 1 below lists various parameters that are referred to subsequently.
For use in both calibration and FOD detection, measurements from the system'"'"'s FOD sensors are communicated to the system controller. Each of the system'"'"'s n sensors typically generates an approximately sinusoidal signal, and the amplitude r and phase θ of the sensor signal is determined by the system controller. The phase of each of the sensor signals can be determined by the controller based on comparison to a reference clock circuit or signal within the controller.
Where signals generated by the system'"'"'s FOD sensors are not approximately sinusoidal, various signal processing techniques can be used by the system controller to determine a fundamental component and/or at least one harmonic component of each of the signals, and the controller can use any combination of fundamental and harmonic components of the signals to determine an amplitude and phase of each of the sensor signals.
From an initial set of N measurements of amplitude and phase from each of the n FOD sensors (with each set of amplitude and phase measurements represented by a vector
The initial mean vector and covariance matrix determined as shown in Equations (1) and (2) above can be calculated as part of the initial system calibration in step 402 of flow chart 400. That is, the system'"'"'s initial calibration state—when no FOD is present in the vicinity of the system—is encoded in the initial mean vector and the initial covariance matrix.
The principal components of the covariance matrix form an orthogonal eigenvector basis set in which all of the FOD sensor measurements can be expressed. Since the covariance matrix represents the variance among FOD sensor measurements, the principal component eigenvectors with the largest associated eigenvalues represent the eigenvector “directions” in the set of FOD measurements along which the variance is highest. Ordering the principal component eigenvectors according to the magnitudes of their associated eigenvalues, the first principal component represents the direction of largest variance in the set of FOD measurements, the second principal component represents the direction of next-largest variance in the set of FOD measurements, and so on. The set of FOD sensor measurements can be represented as a vector projection in the principal component basis with a particular magnitude and direction.
When FOD is introduced in proximity to the system and a new set of FOD sensor measurements are obtained and projected into the principal component basis, the projection representing the new measurements differs from the initial system state described by the original projection. FOD typically perturbs the system away from the initial system state isotropically in all directions because the perturbation represented by the FOD is uncorrelated with other contributions (e.g, global system variations that arise from changes in FOD sensor currents, system noise, environmental changes not caused by FOD such as temperature variations) to variance in the FOD sensor measurements.
Depending upon the nature of the FOD, the perturbation introduced into the measurement signals obtained from the system'"'"'s FOD sensors may be relatively small. In particular, for FOD of relatively small size, and for FOD located at relatively large distances from the FOD sensors, the contribution of the FOD to the variance in the FOD sensor measurements can be minor.
As noted above, the eigenvectors of the covariance matrix with the largest eigenvalues represent the directions in the FOD sensor measurements of largest variance. However, detection of FOD frequently entails measuring the FOD contribution to the variance against what may be a comparatively larger background of variance due to other components and signal contributions in the system. These FOD contributions may therefore more easily be detected by examining the principal components of the covariance matrix with the smallest associated eigenvalues; that is, the principal components that represent the directions of smallest variance in the FOD sensor measurements. The perturbative signal contributions due to FOD are more easily detected against the initial background represented by these principal components.
Equivalently, rather than using the covariance matrix, the methods and systems disclosed herein instead use the inverse covariance matrix to describe the variance in the FOD sensor measurements. The principal components (or eigenvectors) of the inverse covariance matrix with the largest associated eigenvalues represent the directions in the FOD measurement signals with the smallest variance. That is, the principal component of the inverse covariance matrix with the largest associated eigenvalue corresponds to the direction in the FOD sensor measurements along which the variance is smallest, the principal component of the inverse covariance matrix with the next largest associated eigenvalue corresponds to the direction in the FOD sensor measurements along which the variance is next-smallest, and so on. By projecting FOD sensor measurements into a principal components basis derived from the inverse covariance matrix, the presence of FOD in proximity to the system can more readily be identified.
As discussed above, in step 402, an initial system calibration is obtained. The methods disclosed herein allow for an initial calibration state to be quickly generated, the state offering reasonable sensitivity for FOD detection. The initial system calibration can then be refined as the FOD detection algorithm cycles and the inverse covariance matrix is refined.
To obtain an initial system calibration, note first that the diagonal elements of the inverse covariance matrix are simply reciprocals of the variances. The variances can be found by first estimating the mean vectors with a small number of measurements and an infinite impulse response (IIR) filter, as follows:
μt=
The coefficient α, the IIR filter coefficient, weights new information against older information in producing updated mean vectors. In Equation (3), the updated mean vector is computed as a weighted linear combination of new FOD sensor measurements and a previous mean vector. The “half life” of the IIR history is approximately 1/α. For example, a value of α=0.3 and a set of about 5 FOD sensor measurements typically provides a reasonable estimate for the mean vectors. It should be noted that in the discussion that follows, IIR filters are used to update various parameters to account for changes in the values of these parameters over time. More generally, various different types of filters can be used for similar purposes, and the methods are not restricted to the use of IIR filters. The use of such filters is merely discussed for illustrative purposes.
Then, an initial estimate is generated for each of the variances using another IIR filter according to:
where
where σt2 is the i-th signal variance, and Σij−1 is the i,j-th element of the initial inverse covariance matrix. The initial estimate for the inverse covariance matrix computed according to Equations (3)-(6) functions as an initial system calibration. After the initial system calibration has been determined (typically, for example, within a time period of about 1-2 seconds), the system is ready to begin FOD detection.
Referring again to
After the FOD sensor measurements have been obtained in step 404, the next step 404 involves calculation of the FOD detection signal based on the sensor measurements. To calculate the detection signal, the FOD sensor measurements are projected into a principal components basis for the inverse covariance matrix. In general, an orthogonal set of p (where p≤n) principal components are generated from the p eigenvectors of the inverse covariance matrix, sorted in descending order according to the magnitude of the corresponding eigenvalues.
As mentioned above, each principal component encodes the FOD sensor measurements in a global manner, and features contributions from each of the FOD sensor signals. The first step is therefore to find the eigenvectors of the inverse covariance matrix. Specifically, a p×n matrix Φ is constructed, where each column corresponds to a different principal component (e.g., eigenvector) of the inverse covariance matrix, with the eigenvectors ordered in the columns of Φ according to the magnitudes of their respective eigenvectors. To obtain Φ, the system controller performs a partial or complete eigenvector decomposition of the inverse covariance matrix as follows:
Φ=eig(Σ0−1) [7]
Eigenvector decomposition is a well-known mathematical operation and the system controller can use any one of a variety of conventional methods for performing the operation in Equation (7). In practice, it is generally sufficient for FOD detection purposes to obtain only the first few eigenvectors of the inverse covariance matrix (i.e., p=1-6). Thus, Equation (7) can be performed as a partial eigenvector decomposition, reducing the computational load on the system controller. Through experimentation, it has been discovered that determining and using only the first few eigenvectors (i.e., the eigenvectors corresponding to the largest eigenvalues) of the inverse covariance matrix, such that p<<n, generally allows detection of FOD with higher sensitivity than using all eigenvectors as the PC basis, as most of the relevant signal information is contained in the first few eigenvectors.
After the principal components matrix Φ has been obtained, the new FOD sensor measurements—represented by the vector
Pt=(
Principal components analysis generally requires that the data set being analyzed has a zero mean value, which is accomplished by the mean-subtraction in Equation (8). The 1×p matrix Pt now contains the projection or “loading” at time t of the FOD sensor measurements in the principal components basis. The mean vectors
Alternatively, updated mean vectors can also be generated using an IIR filter according to Equation (3), as discussed above.
With the projection Pt of the FOD sensor measurements obtained, detection of FOD can be achieved by processing the FOD sensor measurements directly in the principal components basis. To detect FOD, a scalar detection signal f=F(Pt) is calculated as a function of the principal component loadings.
Various forms off can be used, and the methods disclosed herein do not require a particular functional form. Several examples of suitable FOD detection signals are described below, but it should be understood that other detection signals can also be used.
One type of FOD detection signal that can be used is the L2 norm of Pt, which can be calculated according to:
f=√{square root over (Σi=1p(Pti)2)} [10]
where p≤n principal components are used. This detection signal is effective at detecting FOD because signal measurements that are similar to the calibration and updated signal mean vector will cluster very close to the origin, whereas a perturbation to the magnetic environment caused by FOD will scatter the projection far from the origin.
Another type of FOD detection signal that can be used is a scaled L2 norm of the projection Pt. That is, the projections can be scaled by the eigenvalues of each principal component, effectively normalizing the principal components basis. Scaling the projections in this manner ensures that deviations from the system calibration in each direction along the principal components is weighted equally. In the principal components basis, projections along the principal components are orthogonal and uncorrelated, so weighing them equally can assist in detecting relatively small perturbations that may arise from FOD. The scaled L2 norm can be calculated according to:
where λi is the eigenvalue corresponding to the i-th principal component.
A variety of other FOD detection signals can also be used. In particular, conventional machine learning approaches such as support vector machines, Fisher'"'"'s linear discriminant, and multidimensional decision surfaces in the PC basis can be used to calculate suitable FOD detection signals.
Returning to
ε=a·std(|Pt|) [12]
where a is a scalar constant, and “std” represents the standard deviation. For example, for a positive detection decision when f>ε and with a=5, a correct foreign object detection rate of 95.7% was obtained, with a false positive rate of 1.9% for p=8. For a=3, a correct foreign object detection rate of 98.7% was obtained, but the false positive detection rate increased to 19.6%.
In some embodiments, to minimize false FOD detections and eliminate outlier measurements, a majority-based decision scheme can be used in place of the binary decision discussed above. For example, a buffer containing the most recent m FOD detection signal values f can be maintained by the system controller, and FOD is affirmatively detected only if a majority h of the m values off exceed the detection threshold ε. The probability that a particular value off exceeds ε is given by u=exp(−ε), and thus the false detection rate is given by:
Table 2 shows calculated values of the false detection rate for various majority decision rules corresponding to different buffer lengths m and majority definitions h.
If FOD is detected in step 408, then in step 410, the system controller can optionally take one or more actions. In some embodiments, for example, the system controller can modify one or more system operating parameters. This can include reducing the amount of energy that is transferred between the source and receiver resonators, and even discontinuing energy transfer altogether. In certain embodiments, the system controller can transmit one or more warning messages to users of the wireless energy transfer system. Various optional actions that can be taken will be discussed in greater detail subsequently.
When FOD is not detected in proximity to the system, in step 412, the system calibration is updated before the next FOD detection cycle occurs. Over time, changes in the electromagnetic environment of the system due to factors such as variations in the operating parameters of the source-side power amplifier, local heating, and perturbations due to non-FOD external objects, can lead to significant “drift” from the initial system calibration established at step 402. If the system calibration is not updated to take account of this drift, the FOD false positive detection rate and/or the false negative detection rate can increase.
For vehicle charging applications, significant overall drift has been observed in each of operational modes 1, 2, and 3. The drift may be due to thermal changes in the source-side amplifier, which changes the amplitude of the driving current supplied to the source resonator, leading to drift in the energy transfer magnetic field and induced EMF in the FOD sensors.
In step 412, a variety of different updates to the system calibration and other parameters to account for drift. The mean vector can be updated using an IIR filter as shown in Equation (3) above. The covariance matrix can also be updated in a similar manner using an IIR filter as follows:
Σt=α└(
As discussed briefly above, the IIR filter parameter α governs how quickly the mean vector and covariance matrix are updated. The exponential “half-life” is given by nα, which is related to a as follows:
The rate at which the system updates is generally selected based on two time scales. The first is the characteristic time scale of system drift, which typically occurs at time scales of minutes to hours. The system calibration is generally updated at a rate that is faster than the time scale of drift. The second time scale is the rate at which FOD is introduced in proximity to the system, which generally occurs on the order of a few seconds. The system calibration is generally updated at a rate that is slower than this time scale so that perturbations due to the incoming FOD are not incorporated into the system calibration.
Thus, for a FOD sensing rate of 2 Hz, the product of the sensing rate and nα is 50, which corresponds to a half-life of about 25 seconds. In general, it has been found experimentally that a half-life of about 25-100 seconds for a sensing rate of 2 Hz is appropriate. If the FOD sensing rate is higher (e.g., 10 Hz up to 100 Hz), then the product of the sensing rate and nα can be between 1000 and 10000 (e.g., about 5000), with a relatively small value of α (e.g., α=0.0002).
In general, smaller values of nα are more sensitive to a rapid introduction of FOD, but less sensitive to slow introduction of FOD. To provide sensitivity across a broad range of FOD introduction rates, in some embodiments, the system can obtain FOD sensor measurements corresponding to different a values, so that FOD introduced at virtually any rate in proximity to the system can be detected with high reproducibility.
As discussed above, the methods and systems disclosed herein typically represent FOD sensor measurements in a PC basis derived from the eigenvectors of the inverse covariance matrix. To update the inverse covariance matrix, an updated covariance matrix can first be calculated as shown in Equation (14), and then the updated inverse covariance matrix can be obtained from the updated covariance matrix.
However, other methods can also be used to update the inverse covariance matrix that do not involve performing a matrix inversion operation, which can be time consuming and involve a relatively heavy computational load on the system controller. In particular, when the covariance matrix is updated, if every change to the covariance matrix is an update of rank 1, the Sherman-Morrison-Woodbury formula can be used to calculate an updated inverse covariance matrix. This formula is an exact expression for the inverse of a matrix that is perturbed by a rank 1 update.
For example, suppose matrix M and its inverse M−1 are known at time t−1. If M is perturbed by a rank 1 update corresponding to vt·vt′, such that
Mt+Mt-1+vtvt′ [17]
then an updated inverse, M−1, can be calculated quickly as:
The new inverse matrix can be calculated quickly using Equation (18) because the operations involved are of order O(n2), due to the symmetry of the covariance matrix and the rank 1 outer product update only has n unique entries. As a result, calculation of the inverse matrix is typically faster and more stable numerically than a conventional matrix inversion of order O(n3). Furthermore, because the covariance matrix is symmetric, execution time and storage memory in the system controller can be optimized for performing the update.
To populate the off-diagonal elements in the inverse covariance matrix following the initial calibration and to account for system drift, the covariance matrix can be updated as FOD sensor measurements are acquired. This can be accomplishing by combining the rank 1 update technique of Equation (18) with the IIR filter technique of Equation (14). The IIR filter-based update to can be incorporated directly into Equation (18) as follows:
where vt=
To update the inverse covariance matrix, a value for α is selected. As the covariance matrix is not full rank without N>n and is best