DOUBLE-SIDEBAND SUPPRESSED-CARRIER RADAR TO NULL NEAR-FIELD REFLECTIONS FROM A FIRST INTERFACE BETWEEN MEDIA LAYERS

• US 20080218400A1
• Filed: 10/23/2007
• Published: 09/11/2008
• Est. Priority Date: 10/23/2006
• Status: Active Grant

• Current Assignee: Stolar Incorporated
• Original Assignee: Stolar Incorporated
• Inventors: Bausov, Igor, Stolarczyk, Larry G., Main, Richard B.
• Granted Patent: US 7,656,342 B2
• Time in Patent Office: Days
• US Class Current: 342/22
• CPC Class Codes: E21C 35/24 Remote control specially adapted for machines for slitting or completely freeing the mineral control in general G05
• CPC Class Codes: G01S 13/34 using transmission of continuous, frequency-modulated waves while heterodyning the received signal, or a signal derived therefrom, with a locally-generated signal related to the contemporaneously transmitted signal
• CPC Class Codes: G01S 13/885 for ground probing prospecting or detecting using electromagnetic waves G01V3/12
• CPC Class Codes: G01S 7/02 of systems according to group G01S13/00
• CPC Class Codes: G01S 7/4052 by simulation of echoes
• CPC Class Codes: G01S 7/4056 specially adapted to FMCW
• CPC Class Codes: G01S 7/4082 using externally generated reference signals, e.g. via remote reflector or transponder
• CPC Class Codes: G01V 3/12 operating with electromagnetic waves operating with millimetre waves G01V8/005

Abstract

A ground-penetrating radar comprises a software-definable transmitter for launching pairs of widely separated and coherent continuous waves. Each pair is separated by a constant or variable different amount double-sideband suppressed carrier modulation such as 10 MHz, 20 MHz, and 30 MHz Processing suppresses the larger first interface reflection and emphasizes the smaller second, third, etc. reflections. Processing determines the electrical parameter of the natural medium adjacent to the antenna.

The modulation process may be the variable or constant frequency difference between pairs of frequencies. If a variable frequency is used in modulation, pairs of tunable resonant microstrip patch antennas (resonant microstrip patch antenna) can be used in the antenna design. If a constant frequency difference is used in the software-defined transceiver, a wide-bandwidth antenna design is used featuring a swept or stepped-frequency continuous-wave (SFCW) radar design.

The received modulation signal has a phase range that starts at 0-degrees at the transmitter antenna, which is near the first interface surface. After coherent demodulation, the first reflection is suppressed. The pair of antennas may increase suppression. Then the modulation signal phase is changed by 90-degrees and the first interface signal is measured to determine the in situ electrical parameters of the natural medium.

Deep reflections at 90-degrees and 270-degrees create maximum reflection and will be illuminated with modulation signal peaks. Quadrature detection, mixing, and down-conversion result in 0-degree and 180-degree reflections effectively dropping out in demodulation.

Claims

11. An earth-penetrating radar method, comprising:

using a near measurement mode and a far measurement mode for predistortion and calibration of a transmitted waveform and a carrier suppression;

setting a radar first to near measurement mode to measure near-antenna signals reflected from a first interface by setting a phase of a modulation signal to θ

m to 0 (π

) during a calibration;

processing a near measurement mode, wherein a first sideband is tuned off and a magnitude and phase are a measurement of a second sideband alone;

repeating a measurement for an opposite sideband;

adjusting magnitudes of said sidebands to be equal in value and adjusting the phase θ

m to produce 0-degrees;

adjusting θ

c is adjusted to zero to compensate for a frequency response in the radar and antennas;

then switching to a far measurement mode that sets

$\mathrm{\theta <br><br>}<br><br><br><br>m=\frac{\mathrm{\pi <br><br>}}{2}<br><br><br><br>\mathrm{or}<br><br><br><br>\frac{3<br><br><br><br>\mathrm{\pi <br><br>}}{2}$

such that any first interface reflection is suppressed

using polarized antennas for any additional suppression; and

using a software-defined transceiver for phase-coherent detection of the depth of said second interface reflection.

1. An earth-penetrating radar, comprising:

a radar transmitter for launching pairs of separated and coherent continuous waves in a double-sideband suppressed-carrier modulation through the air;

a radar receiving antenna for placement proximate to an air interface with a first layer of material, and having impedance characteristics that depend on a surrounding natural medium adjacent to the antenna and an operating frequency;

a radar receiver with coherent demodulation for suppressing a first reflection of radio signals emitted by the radar transmitter from an air interface with a first layer of material and received by the radar receiving antenna;

a receiver processor for determining any electrical parameters of the natural medium adjacent to the antenna from stored a priori data and impedance measurements of the radar receiving antenna;

a radar processor for calculating the depth of an interface between said first layer of material and a second deeper layer of material, by measuring a signal delay of a second reflection of radio signals emitted by the radar transmitter from said first and second material interface which was received by the radar receiving antenna;

2. The radar of claim 1, wherein:

the whole is mounted to a coal-cutting drum on a mining machine;

said first layer of material comprises coal; and

said second layer of material comprises at least one of water, boundary rock, and voids.

3. The radar of claim 1, further comprising:

a software-defined radio transceiver with program software to implement the radar transmitter and radar receiver, wherein a software programming enables a switch in operational modes between near-field and far-field signal detection.

4. The radar of claim 3, further comprising:

a modulation process for generating a frequency difference between pairs of frequencies in launched waves;

wherein, if a variable frequency is used by the software-defined transceiver, then pairs of tunable resonant microstrip patch antennas are included;

wherein, if a constant frequency difference is used by the software-defined transceiver, then a wide-bandwidth antenna is included with a swept or stepped-frequency continuous-wave (SFCW) function.

5. The radar of claim 1, wherein:

the radar receiver accepts a received modulation signal with a phase range that starts at 0-degrees at a radar transmitter antenna, and suppresses said first reflection after coherent demodulation, then the modulation signal phase is changed by 90-degrees by the radar transmitter and said first reflection is measured again to determine in situ electrical parameters of any intervening natural medium.

6. The radar of claim 1, wherein:

the radar Transmitter and receiver use deep reflections at 90-degrees and 270-degrees phase to create maximums in reflections that will be illuminated with modulation signal peaks, and the radar receiver uses quadrature detection, mixing, and down-conversion result in 0-degree and 180-degree reflections effectively to drop out such demodulation.

7. The radar of claim 1, further comprising:

a software-definable transceiver programmed as a geologic media penetrating radar with a direct digital synthesizer (DDS) for synthesizing pairs of many coherent first and second continuous waves (CW) with frequencies of ω

o−

ω

i, and ω

o+ω

2 etc., as individual pairs separated in frequency by a constant or variable frequency difference;

wherein, said pairs of continuous waves create a double-sideband, suppressed-carrier waveform, and the suppressed carrier may be held constant, swept, or stepped in frequency (ω

o) across the operating frequency range of the radar.

8. The radar of claim 7, wherein:

said suppressed carrier and modulation signal magnitudes and phases are software controlled, the suppressed carrier phase is θ

c and the modulation phase is θ

m, and a difference in frequency between the sidebands ω

o−

ω

1, ω

o+ω

2 is the modulation frequency

${\mathrm{\omega <br><br>}}_m=\frac{{\mathrm{\omega <br><br>}}_2+{\mathrm{\omega <br><br>}}_1}{2}.$

9. The radar of claim 7, further comprising:

a circuit to prevent spurious signals from conflict with the mixed-down intermediate frequency (intermediate frequency) amplifier passband signal, wherein, ω

o−

ω

1, ω

o+ω

2, ω

2 and ω

1, and heterodyne frequencies ω

3 and ω

4 are each outside the passband of any intermediate amplifier (ω

IF≠

ω

m, ω

1, ω

2, ω

3, and ω

4).

10. The radar of claim 7, further comprising:

an intermediate amplitude band pass center frequency ω

_IF=ω

₄−

ω

₂=ω

₁−

ω

₃, wherein, ω

2≠

ω

1 and ω

3≠

ω

4, the suppressed carrier frequency,

${\mathrm{\omega <br><br>}}_{\mathrm{cm}}=\frac{{\mathrm{\omega <br><br>}}_2-{\mathrm{\omega <br><br>}}_1}{2}+{\mathrm{\omega <br><br>}}_0$

and the heterodyne frequency is

${\mathrm{\omega <br><br>}}_{\mathrm{cH}}=\frac{{\mathrm{\omega <br><br>}}_4-{\mathrm{\omega <br><br>}}_3}{2}+{\mathrm{\omega <br><br>}}_0,$

and a distance to any target continues in the phase terms ω

mτ and

ω

cmτ

.

12. The earth-penetrating radar method of claim 11, further comprising:

dynamically predistorting each of a pair of first and second continuous waves'"'"' magnitude and phase to account for frequency response nonlinearities with a feedback-enabled predistorter when operating in a near measurement mode.

13. The earth-penetrating radar method of claim 12, further comprising:

predistorting any received waveform phase by computing an inverse tangent of an intermediate-frequency signal in phase (I) and quadrature (Q) components and then dividing by ω

cm;

wherein, θ

c measured and set to cause θ

c+ω

cmτ

to be zero so a first interface reflection will occur at τ

=0.

13-1. The earth-penetrating radar method of claim 12, further comprising:

predistorting a modulation phase by first measuring a magnitude of an intermediate frequency signal as a predistorted waveform suppressed carrier frequency is incremented in any FMCW or SFCW radar operating frequency range; and

solving simultaneous equations for cos(ω

mτ

) and a range to a target.

14. An earth-penetrating radar, comprising:

a power amplifier and antenna for launching corrected versions of coherent pairs of said first and second continuous wave frequencies into a geologic heterogeneous media with different constituent electrical parameters for causing first, second, etc. interface reflected waves to be received;

a receiver and antenna for collecting signals reflected from a first interface and other signals reflected or scattered from buried objects and interfaces of material with contrasting electrical parameters;

a down-converter and coherent demodulator for coherent demodulating of an in-phase I=cos(θ

m+ω

mτ

1)cos(θ

c+ω

cmτ

1)+cos(θ

m+ω

cmτ

2)cos(θ

cm+ω

cτ

2)+ . . . , and Q=cos(θ

m+ω

mτ

1)sin(θ

c+ω

chτ

1)+cos(θ

m+ω

mτ

2)sin(θ

c+ω

cmτ

2)+ . . . , where ω

m is a processor-controllable phase shift (π

/2, 0, 3π

/2, 2π

), . . . , ω

m is the modulation frequency of a double-sideband suppressed carrier or phase-modulated signal, and θ

c is a carrier phase with a frequency of ω

cm;

a processor for determining the magnitude of each reflection as M=|cos(θ

_m+ω

_mτ

)| for each pair of transmitting continuous waves, wherein τ

1 represents the echo delay time occurring for reflections from the surface near the antenna and τ

2 represents the echo delay time occurring for more distant reflections from buried objects and interfaces;

a device for predistortion that results in a modulation signal phase θ

m being set to zero when π

1=0 in a far measurement mode calibration process, and a predistorted modulation signal phase is set to a near measurement mode and then measured in a far measurement mode to determine a distance (R) to a second interface by measuring ω

mτ

in the intermediate frequency.

15. The radar of claim 14, further comprising:

a processor for maximizing a magnitude (M), wherein, a second interface or object reflection from a location, R=λ

m/8, where λ

m=c/f_m×

√

{square root over (∈

_r)} (c is 3×

108 meters per second) and fm is the modulation frequency.

16. The radar of claim 14, further comprising:

a switch for applying FMCW radar if an allowable measurement time for a SFCW radar is too short;

wherein, if a boundary or target object is less than one-half a suppressed-carrier wavelength away from a pair of antennas, a DSB suppressed carrier frequency is set to a constant carrier frequency, ω

cm, and if a boundary object is more than λ

/2, a swept- or stepped-frequency radar is applied.