Circuit arrangement for accurately and effectively driving an ultrasonic transducer

• US 5,113,116 A
• Filed: 10/05/1989
• Issued: 05/12/1992
• Est. Priority Date: 10/05/1989
• Status: Expired due to Fees

• Current Assignee: Eberspacher Exhaust Technology GmbH & Company KG
• Original Assignee: Firma J. Eberspacher
• Inventors: Wilson, Robert F.
• Primary Examiner(s): BUDD, MARK OSBORNE
• Application Number:
  US07/417,295
• Time in Patent Office: 950 Days
• Field of Search: 310/316, 310/317, 318/116
• US Class Current: 310/316.01
• CPC Class Codes: B06B 1/0253 taken directly from the generator circuit
• CPC Class Codes: B06B 2201/77 Atomizers

Abstract

A method for driving an ultrasonic transducer, intended for use in atomization of liquids, at one of its selected resonance frequencies, by tuning out the capacitance of the ultrasonic transducer by means of an inductor, by sensing the transducer current, by comparing the phases of the transducer driving voltage and the transducer current and by controlling a voltage controlled oscillator for driving the ultrasonic transducer, by means of a phase error signal such that the ultrasonic transducer is driven with a frequency at which the transducer driving voltage and the transducer current are in phase, whereby the transducer driving circuit is locked to a natural resonance frequency of the ultrasonic transducer.

Claims

1. A method for driving an ultrasonic transducer, intended for use in atomization of liquids, at a selected one of its resonance frequencies, comprising:

parallely tuning out, at the selected resonance frequency, an intrinsic capacitance of said ultrasonic transducer by shunting said transducer by a tuning impedance by connecting said tuning impedance in parallel with said transducer;

applying a driving voltage signal to the transducer;

sensing a resulting current signal through the transducer;

comparing the phases of the driving voltage and the resulting current signals;

and changing the frequency of the driving voltage signal until said driving voltage and resulting current signals are in phase.

2. A method according to claim 1, where a phase locked loop is used and the frequency of the driving voltage signal is changed until said driving voltage and resulting current signals are locked in phase.

3. A method according to claim 2, where the phase locked loop provides a high DC gain to force a constant phase difference between the compared phases of the driving voltage and the resulting current signals so that the phase relationship of the driving voltage and the resulting current signals does not vary with changing the transducer resonance frequency and the transducer is always driven at its resonance frequency even though this resonance frequency may change.

4. A method according to claim 1, wherein a substantially constant power output is achieved by using a constant output current.

5. A method according to claim 1, wherein said tuning impedance is an inductor.

6. A circuit arrangement for driving an ultrasonic transducer adapted to be used for atomization of liquids, at a selected one of its resonance frequencies comprising:

a parallel connected tuning means, including a tuning impedance, connected in parallel with said transducer so as to shunt said transducer, for tuning out, at a selected resonance frequency, an intrinsic capacitance of said ultrasonic transducer so that at the selected resonance frequency a transducer driving voltage and a transducer current are in phase;

voltage controlled oscillator means having an oscillator input and an oscillator output coupled for driving said ultrasonic transducer with said transducer driving voltage;

current sensor means for sensing said transducer current;

phase comparator means, having two comparator inputs and a comparator output, for comparing the phases of said transducer driving voltage and said transducer current, a first one of said two comparator inputs being coupled to receive a voltage signal being proportional in phase to said transducer driving voltage and the other one of said two comparator inputs being coupled to receive a current signal from said current sensor means, the current signal being proportional in phase to said transducer current;

an output signal of said phase comparator means being coupled to cause said voltage controlled oscillator means to output a frequency at which the transducer driving voltage and the transducer current are in phase, whereby said circuit arrangement is locked to said selected resonance frequency.

7. A circuit arrangement according to claim 6, further comprising a linear phase low pass filter means coupled between said current sensor means and said second comparator input, the low pass filter with linear phase reponse being used as a means of extracting a fundamental frequency without additional frequency dependent phase shift, from a complex transducer current signal wave form that results from driving a transducer with a voltage signal including harmonics of the fundamental frequency.

8. A circuit arrangement according to claim 6, where said comparator output is coupled to said oscillator input through a low pass filter means.

9. A circuit arrangement according to claim 8, where said phase comparator means comprises a phase detector that outputs a frequency sum and a frequency difference of frequencies of input signals coupled to the first and the second comparator inputs, respectively, and where said low pass filter means removes the sum frequency so that said low pass filter means outputs a DC signal.

10. A circuit arrangement according to claim 9, where said low pass filter means has a high DC gain.

11. A circuit arrangement according to claim 10, where the DC gain of said low pass filter means is at least about 50 dB.

12. A circuit arrangement according to claim 11, where the DC gain is about 100 dB.

13. A circuit arrangement according to claim 8, where said low pass filter means comprises an integrator means.

14. A circuit arrangement according to claim 13, where said integrator means comprises a high DC gain amplifier.

15. A circuit arrangement according to claim 14, where said high DC gain amplifier comprises an operational amplifier having an inverting input, a non-inverting input and an amplifier output, said inverting input being coupled to receive said output signal from said phase comparator means, said non-inverting input being coupled to a reference voltage source and the amplifier output being coupled to said oscillator input and, through a capacitor, to said inverting input.

16. A circuit arrangement according to claim 6, where said oscillator output is coupled to said ultrasonic transducer by means of a power amplifier.

17. A circuit arrangement according to claim 6, where said oscillator output is coupled to said ultrasonic transducer by means of a transformer.

18. A circuit arrangement according to claim 6, where said first comparator input is coupled to said oscillator output.

19. A circuit arrangement according, to claim 6, where said phase comparator means comprises a multiplying type analog phase detector, and a -90°

phase shifting means is coupled between the output of said voltage controlled oscillator means and said first comparator input of said phase comparator means.

20. A circuit arrangement according to claim 6, wherein said phase comparator means comprises a phase detector that requires a square wave input.

21. A circuit arrangement according to claim 9, where a circuit means producing a square wave output is coupled between said current sensor means and said second comparator input.

22. A circuit arrangement according to claim 6, where a threshold amplifier is coupled between said current sensor means and said second comparator input,

the threshold amplifier having a predetermined signal passing threshold being selected such that the threshold amplifier blocks the passage to said phase comparator means of low level signals being below a predetermined threshold, the level of which is selected to be higher than an output signal from the current sensor means caused when said ultrasonic transducer is in parallel resonance.

23. A circuit arrangement according to claim 6, being adapted to output a square wave transducer driving voltage, where a linear phase low pass filter means is coupled between said current sensor means and said second comparator input, the low pass filter with linear phase response being used as a means of extracting the fundamental frequency without additional frequency dependent phase shift, from the complex transducer current signal waveform that results from driving a transducer with a squarewave voltage signal.

24. A circuit arrangement according to claim 6, wherein said tuning impedance, which is connected in parallel with said transducer, comprises a tuning inductor.

25. A circuit arrangement for driving an ultrasonic transducer adapted to be used for atomization of liquids, at a selected one of its resonance frequencies, comprising:

tuning means for tuning out, at a selected resonance frequency, an intrinsic capacitance of said ultrasonic transducer so that at the selected resonance frequency a transducer driving voltage and a transducer current are in phase;

voltage controlled oscillator means having an oscillator input and an oscillator output coupled for driving said ultrasonic transducer with said transducer driving voltage;

current sensor means for sensing said transducer current;

phase comparator means, having two comparator inputs and a comparator output, for comparing the phases of said transducer driving voltage and said transducer current, a first one of said two comparator inputs being coupled to receive a voltage signal being proportional in phase to said transducer driving voltage and the other one of said two comparator inputs being coupled to receive a current signal from said current sensor means, the current signal being proportional in phase to said transducer current;

an output signal of said phase comparator means being coupled to cause said voltage controlled oscillator means to output a frequency at which the transducer driving voltage and the transducer current are in phase, whereby said circuit arrangement is locked to said selected resonance frequency;

first controllable switch means having a first switch control input and being coupled between said voltage controlled oscillator means and said ultrasonic transducer, for intermittently connecting said ultrasonic transducer to said oscillator output; and

pulse width modulator means coupled between said first switch control input and said current sensor means, for outputting switch control pulses, the duty cycle of which is a function of an actual level of an output signal from said current sensor means such that the width of said switch control pulses is larger the smaller is the level of said output signal from said current sensor means.

26. A circuit arrangement according to claim 25, where the first controllable switch means comprises a switchable power amplifier coupled between said voltage controlled oscillator means and said ultrasonic transducer.

27. A circuit arrangement according to claim 25, further comprising:

an integrating low pass filter means having a filter input and a filter output and being coupled between said comparator output and said oscillator input;

and a second controllable switch means having a second switch control input and being coupled between the phase comparator output and the filter input;

said second switch control input being coupled to receive said switch control pulses from said pulse width modulator means, for disconnecting said filter input from said comparator output when said first controllable switch means disconnects said ultrasonic transducer from the oscillator output.

28. A circuit arrangement according to claim 25, where the width of the pulses from said pulse width modulator is a multiple of the period of said transducer driving voltage at the selected resonance frequency so that said ultrasonic transducer is driven in a burst mode.

29. A circuit arrangement for driving an ultrasonic transducer adapted to be used for atomization of liquids, at a selected one of its resonance frequencies, comprising:

tuning means for tuning out, at a selected resonance frequency, an intrinsic capacitance of said ultrasonic transducer so that at the selected resonance frequency a transducer driving voltage and a transducer current are in phase;

voltage controlled oscillator means having an oscillator input and an oscillator output coupled for driving said ultrasonic transducer with said transducer driving voltage;

current sensor means for sensing said transducer current;

phase comparator means, having two comparator inputs and a comparator output, for comparing the phases of said transducer driving voltage and said transducer current, a first one of said two comparator inputs being coupled to receive a voltage signal being proportional in phase to said transducer driving voltage and the other one of said two comparator inputs being coupled to receive a current signal from said current sensor means, the current signal being proportional in phase to said transducer current;

an output signal of said phase comparator means being coupled to cause said voltage controlled oscillator means to output a frequency at which the transducer driving voltage and the transducer current are in phase, whereby said circuit arrangement is locked to said selected resonance frequency;

a sweep generator having a generator input and a generator output and being coupled to control said voltage controlled oscillator means to sweep its frequency between the limits of its predetermined frequency range;

a controllable sweep switching means having a sweep switch control input and being coupled between said sweep generator and said oscillator input;

an auxiliary phase comparator means for outputting a sweep switch control signal, and having two auxiliary phase comparator inputs and an auxiliary phase comparator output;

a first one of said two auxiliary phase comparator inputs being coupled to receive said voltage signal being phase-proportional to said transducer driving voltage and a second one of said two auxiliary phase comparator inputs being coupled to receive said current signal being phase-proportional to said transducer current;

the auxiliary phase comparator output being coupled to said sweep switch control input for connecting the sweep generator output to said oscillator input when a difference of the phases of the signals at said two auxiliary phase comparator inputs reaches a predetermined threshold.

30. A circuit arrangement according to claim 29, further comprising a threshold detector coupled between said auxiliary phase comparator output and said switch control input.

31. A circuit arrangement according to claim 29, further comprising a resettable time delay means coupled between said auxiliary phase comparator output and said switch control input and is adapted to pass said switch control signal only if the time length of said switch control signal is larger than a predetermined delay time period.

32. A circuit arrangement according to claim 30, further comprising:

a second controllable switch means having a second switch control input and being coupled between said voltage controlled oscillator means and said ultrasonic transducer, for intermittently connecting said ultrasonic transducer to said oscillator output;

and a pulse width modulator means coupled between said second switch control input and said current sensor means, for outputting switch control pulses, the duty cycle of which is in response to an actual level of an output signal from said current sensor means such that the width of said switch control pulses is larger the smaller is the level of said output signal from said current sensor means,

wherein the width of the pulses from said pulse width modulator is a multiple of the period of said transducer driving voltage at the selected resonance frequency so that said ultrasonic transducer is driven in a burst mode, and

wherein the predetermined delay time period is selected to be longer than the maximum interruption between two subsequent pulses from said pulse width modulator.

33. A circuit arrangement according to claim 32 wherein the auxiliary phase comparator output is also coupled to a disconnect switch control input for opening a second controllable disconnect switch means when said sweep generator means is connected to said oscillator input.

34. A circuit arrangement according to claim 29, wherein said comparator output is coupled to said oscillator input through a low pass filter,

said low pass filter means comprises an integrator having a high DC gain amplifier,

said high DC gain amplifier comprises an operational amplifier having an inverting input, a non-inverting input and an amplifier output, said inverting input being coupled to receive said output signal from said phase comparator means, said non-inverting input being coupled to a reference voltage source and the amplifier output being coupled to said oscillator input and, through a capacitor, to said inverting input,

and the generator input and the generator output are coupled to said inverting input of said operational amplifier during a sweeping operation.

35. A circuit arrangement according to claim 34, wherein the sweep generator comprises:

a current source means adapted to be switched between drawing a relatively low current from the input of the integrator means and supplying a relatively high current into the input of the integrator means,

and a voltage comparator means for detecting a start of an increase of the voltage at the input of the integrator means;

the current source means being controllable to draw said low current at the beginning of a sweeping operation and upon detection of said start of increase and to supply said high current upon detection of said start of decrease.